Cambridge Audio azur 840A Quick reference guide

White paper
February 2006
Cambridge Audio 840A Class XD™ integrated amplifier
Matthew Bramble – Technical Director, Cambridge Audio
Douglas Self – Electronic Engineer, Cambridge Audio
Cambridge Audio made a significant leap forward
with the introduction of the Azur range in 2003 by
pushing the boundaries of what was possible in
the budget audiophile segment of the market.
However, we were also keen to produce a high-end
product range which allowed us to flex our engineering muscles and show what we can do with
fewer constraints. A number of development programmes burgeoned while working on the original
and V2 Azur ranges of which the 840A Class XDTM integrated amplifier was one, part of our new 8-
Series.
A number of ideas came to the fore, including the implementation of full microprocessor control for
all functions, nameable inputs and AV mode, custom install features such as RS232 and outputs
for our own Incognito multi-room system. But above all, the unit had to be a true audiophile product
in that sound quality was paramount.
We decided the 840A should in fact be a pre-amplifier and dual-mono power amplifier all in one
chassis. It should also have a balanced input for the matching CD player (of which more in a
separate white paper), two pairs of very high current output transistors per channel so it could drive
any speaker, a new acoustically damped casework and relay switching for input selection. A
relay/resistor ladder volume control scheme for excellent channel balance and low distortion was
also designed.

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Cambridge Audio prides itself on employing the finest staff and we are lucky enough to have
Douglas Self, the renowned writer, designer and amplifier researcher working in our engineering
team. When Doug joined us he already had the seed of an idea to develop a new amplifier topology
and it wasn’t long before he’d pitched us his ‘brave new idea’ and what was to become the Class
XD™ development programme began. The 840A is the first ever Class XD product and the result of
over two years development work.
This new patent-pending technology is only a part of the 840A but is significant enough to warrant
separate treatment here, this white paper aims to outline Class XD technology in simple terms.
Please bear in mind this paper is by its nature technical in style and does not cover the many other
small circuits and tweaks developed as part of the 840A’s extensive measurement and listening
test programme.
For a more in depth technical description of Class XD, please refer to our UK Patent application
number GB 0505024.0.
Background: The state-of-the-art
The great divide in solid-state amplifier technology has always been between the efficient
but ultimately compromised Class B approach and the beautifully linear but dishearteningly
inefficient Class A.
The basic difference between the two methods being that in Class A the output transistors are
modulated by the audio signal to turn more or less ‘on’ but never actually turn off, in Class B the
output transistors actually at some point turn off as the output is passed from one transistor to
another. It is at the point at which the output moving from one transistor to another (the crossover
point) that a small amount of distortion is created. This ‘crossover distortion’ is inevitable and
although it can be minimized, it can be shown that it cannot be completely eliminated. Class A of

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course avoids this small pitfall (because the transistors are always on) but at the expense of a lot
of heat generation. Managing this heat and power dissipation inevitably means that Class A
designs are much more expensive to implement and often of lower power output so as to minimise
the heat as much as possible.
It is indisputable that Class A power amplifiers have the potential to give the best linearity when
well designed, but they are usually impracticable, in reasonably priced equipment at least.
Alternatively, optimal Class B linearity can of course be very good when well designed and is the
preferred method we and most other amplifier designers use in our core products.
We won’t cover these two design methodologies in more detail here as they are generally well
understood and covered in other sources. It is important that it should not be assumed that in
doing this work we intended to replace the Class B or A approaches, both have very real
advantages at different ends of the market and both can be made to sound wonderful when well
implemented. What we were seeking with the development of Class XD was a way of incorporating
a lot of the advantages and sound quality of Class A at a far lower price level than normal and
without the inefficiency inherent in that method.
Well designed Class B amplifiers can in fact achieve extremely low distortion levels of <0.001%-at 1
kHz [Ref 2]. The Class B approach however, does have its ultimate limitations, as we have said
Class B inherently generates crossover distortion, and inconveniently displays this non-linearity at
the zero-crossing, where it is always in evidence no matter how low the signal amplitude. At one
unique value of quiescent current the distortion produced is a minimum, and this is what
characterises optimal Class B; however at no value can it be made to disappear. It is in fact
inherent in the classical Class B operation of a pair of output transistors.
Fig 1 shows a simulation of an output stage that illustrates the heart of the ‘problem’. The diagram
plots the incremental gain of the output stage against output voltage; in other words the gain for a
very small signal. A complementary-feedback pair (CFP) output stage was used. Both 8 and 4 Ohm

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loads are shown. You can see from the Y-axis that in the 8 Ohm case in particular, the gain
variations are very small, with an inoffensive-looking gain ripple around the zero-crossing at 0V
output. This gain ripple however does generate high-order harmonics that can be poorly linearised
as the negative-feedback factor in any linear amplifier falls with increasing frequency.
The 4 Ohm case shows lower overall gain due to the increased loading, and a drop-off of gain at
each side due to falling transistor beta (current gain); this latter distortion mechanism is however
relatively easy to deal with by the use of negative feedback and other methods, and is not
considered further. The awkward gain perturbations at the crossover point are similar to the 8 Ohm
case, but can be seen to be larger in size.

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Fig 1: The incremental gain of a CFP output stage as output voltage changes. SPICE (Simulation
Program with Integrated Circuit Emphasis) for 8 and 4 Ohm loads.
There has always been a desire for a compromise between the efficiency of Class B and the
linearity of Class A and the most obvious way to make one is to turn up the quiescent current of a
Class B stage giving what is called Class AB operation. As this is done, an area of Class A
operation, with both output transistors conducting, is created around the zero-crossing.
In fact as this area widens as the quiescent current increases, until ultimately it encompasses the
entire voltage output range of the amplifier, there is thus an infinite range of positions between the
two extremes of Class B and Class A, and this range of modes of operation is referred to as Class
AB.
Unfortunately, while Class AB would seem to be a perfect compromise between Class A and Class
B operation, it does have some hidden issues.
It can be shown [Ref 1] that if Class AB is used to trade-off between efficiency and linearity, its
performance is certainly superior to B below the AB transition level, operating as it does in this
region in pure Class A. This can have very low THD indeed, at less than 0.0006% up to 10 kHz [Ref
3].
However, once the signal exceeds the limits of the Class A region, the THD worsens and does so
somewhat abruptly due to the gain-changes when the output transistors turn on and off. Linearity is
in fact inferior not only to Class A but also to optimally-biased Class B. This is not always fully
appreciated. The effect is sometimes called "gm-doubling".
Class AB distortion can be made very low by good design, but remains at least twice as high as for
the equivalent Class B situation. The bias control of a Class B amplifier actually does not give a
straightforward trade-off between power dissipation and linearity at all levels; this is often not well

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understood and often catches out the unwary. To demonstrate this, Fig 2 shows THD plotted
against output level for Classes AB and B.
Fig 2: THD vs. level for Class B and Class AB. (0 dB is 30W into 8 Ohms)
So actually it would be much more desirable to have an amplifier that would give Class A
performance up to the transition level, with Class B after that, rather than AB. This would abolish
the AB gain changes that cause the extra distortion. This was the purpose of our Class XD
development program, could it be done?
The Class XD crossover displacement principle
We can see that in Class B it would be better if the crossover region were anywhere else rather
than where it is. If the crossover were displaced away from its zero-crossing position, then the
amplifier output would not traverse it until the output reaches a certain voltage level. Also below
this transition point the performance could be pure Class A; above it the performance normal Class
B.

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This is the basic Class XD principle, and it’s a very simple one, develop a topology that displaces
the crossover point to one side of zero crossing.
The essence of the Crossover Displacement principle is the injection of an extra current, into the
output point of a conventional Class B amplifier. This is shown in Fig 3.
Fig 3: On the left is a conventional Class B output stage, showing drivers and bias voltage source.
At the right the stage has been modified by adding a displacer system that draws current from the
output and sinks it into the negative rail.
For convenience we have called the current-injection subsystem The Displacer. Similarly the upper
transistor is The Source, while the lower is The Sink. The displacement current does not directly
alter the voltage at the output - the output stage inherently has low output impedance, and this is
further lowered by the use of global negative feedback. What it does do is alter the pattern of
current flowing in the output devices. The displacement current in the version shown here is sunk to
V- from the output, rather than sourced from V+, so the crossover region is displaced downward
rather than being pulled upwards. This is arbitrary as the direction of displacement makes no
difference, either could be used.

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The extra current therefore flows through Re1, and the extra voltage drop across it means the
output voltage must go negative before the current through Re1 stops and that in Re2 starts. In
other words, the crossover point when Q3 hands over to Q4 has been moved to a point negative of
the 0V rail; for the rest of this article we refer to this as the “transition point”. For output levels
below transition no crossover distortion is generated. The resulting change in the incremental gain
of the output stage is shown in Fig 4.
The displacer current could of course be constant, or, as we then developed in more sophisticated
implementations could even vary with the signal…
We now have before us the intriguing prospect of a power amplifier with three output devices, which
if nothing else is novel. The operation of the output stage is inherently asymmetrical, and in fact
that is its raison d’être, but this should not cause undue alarm. Circuit symmetry is often touted as
being a pre-requisite for either low distortion or healthy operation in general, but this has no real
basis in fact. A perfectly symmetrical circuit may have no even-order distortion, but it may still have
any amount of odd-order non-linearity, such as a cubic characteristic. Odd-order harmonics are
normally considered more dissonant and often more noticeable and deleterious to perceived sound
quality in listening tests, so circuit symmetry in itself is not a useful goal.

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Fig 4: SPICE simulation of the output stage gain variation with and without a constant 1Amp of
displacement current. The central peak is moved left from 0V to -8V.
Realisation
There are several ways in which a suitable displacement current can be drawn from the main
amplifier output node.
Resistive crossover displacement
The most straightforward way to implement crossover displacement would be to simply connect a
suitable power resistor between the output rail and a supply rail, as shown in Fig 5.

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Fig 5: The concept of resistive crossover displacement. In and the following cases, the crossover
point is displaced positively by sinking a current into the negative rail.
This method suffers from poor efficiency, as the resistance acts as another load on the amplifier
output, effectively in parallel with the normal load. It also threatens ripple-rejection problems as R is
connected directly to a supply rail, which in most cases is unregulated and carrying substantial 100
Hz ripple. A regulated supply to the resistor could be used, but this would be very uneconomic and
even less efficient due to the voltage drop in the regulator. The resistive system is inefficient
because the displacement of the crossover region occurs when the output is negative of ground,
but when the output is positive the resistor is still connected and greater current is drawn from it as
the voltage across it increases. This increasing current is of no use in the displacement process
and simply results in increased power dissipation in the positive output half-cycles.