Oakley Filtrex II User manual

Oakley Sound Systems
Filtrex II
PCB issue 2
Analogue Filter Rack
Builder's Guide
V2 4
Tony Allgood
Oakley Sound Systems
Carlisle
United Kingdom

Introduction
This is the Builder's Guide for the issue 2 iltrex II rack module from Oakley Sound. It
contains the schematic description, parts list and testing procedures. or those of you with an
issue 1 iltrex-II board you should ensure that you have the proper Builder's Guide for your
board and not this one.
or the User Manual, which includes a brief history about the development of the module, a
guide to the front panel controls and some notes about the power pack needed to power your
module, please visit the project webpage at:
http://www.oakleysound/filtrex.htm
or general information regarding where to get parts and suggested part numbers please see
our useful Parts Guide at the project webpage or http://www.oakleysound.com/parts.pdf.
or general information on how to build our modules, including circuit board population,
mounting front panel components and making up board interconnects please see our
Construction Guide at the project webpage or http://www.oakleysound.com/construct.pdf.
This is an early version of the documentation. If you do find any errors, even silly little ones,
please do let me know either directly by e-mail or via the orum or mailing list.
2

Parts List
or general information regarding where to get parts and suggested part numbers please see
our useful Parts Guide at the project webpage or http://www.oakleysound.com/parts.pdf.
The components are grouped into values, the order of the component names is of no particular
consequence.
A quick note on European part descriptions. R is shorthand for ohm. K is shorthand for kilo-
ohm. R is shorthand for ohm. So 22R is 22 ohm, 1K5 is 1,500 ohms or 1.5 kilohms. or
capacitors: 1u = one microfarad = 1000n = one thousand nanofarad.
To prevent loss of the small ‘.’ as the decimal point, a convention of inserting the unit in its
place is used. eg. 4R7 is a 4.7 ohm, 4K7 is a 4700 ohm resistor, 6n8 is a 6.8 n capacitor.
Please note that if you are building a stereo version of this module you will need two
Filtrex-II boards One of them will be built as a Master and the other as a Slave For the
Slave module you should not fit parts marked with a * Please see later in this
document for a suggested method on how to wire the two modules together
Resistors
All resistors 5% or better 0.25W types. Those items marked with 1% need to be 1% metal
film (or better) 0.25W metal film resistors. or the sake of clarity it may be simpler to make all
resistors 1% metal film types.
R61 is a +3000ppm/K positive temperature coefficient resistor.
22R R5, R53, R109, R4, R52, R115, R121, R96, R80, R81, R8, R122
47R R111, R116, R126
150R, 1% R51, R54
330R R10, R18, R19, R13, R17
470R R12, R20
1K R11
1K +3000ppm/K R61
1K5 R117
2K2 R9*, R91, R56, R46, R57
2K2, 1% R25, R24
2K7 R47
3K R100
3K9 R1, R15
4K7 R87, R97, R74
4K7, 1% R41, R43, R30, R34
6K8 R70, R39, R6, R38
10K R123, R3, R78, R58, R113, R55, R104, R110
10K, 1% R42, R32, R31, R44
12K R99
3

15K R40, R37, R69
22K R75, R14, R7, R108, R112
22K, 1% R28, R27, R22, R23
33K R16
39K R107
47K R85, R29, R26, R35, R71, R36, R124, R33, R82, R79
56K R59, R60
68K R65
100K R125, R101, R120, R73, R68, R88, R114, R119, R98, R92, R93, R76,
R72, R84, R89, R95, R94, R118, R66, R67, R64, R45, R83, R103
100K, 1% R48, R50
220K R21, R90, R63
330K R102
470K R62, R49, R2
680K R105
1M R86
3M3 R106, R77
Capacitors
22p low-K 2.5mm ceramic C7, C3
33p low-K 2.5mm ceramic C48, C28
100p low-K 2.5mm ceramic C26
1n , 100V polyester C43, C30, C39
68n , 63V polyester C12, C13, C14, C15
100n , 63V polyester C32, C52, C20, C21, C35, C54, C55, C41, C50*, C38*
470n , 63V polyester C5, C24
680n , 63V polyester C19, C18, C17, C44
1u , 63V polyester C16
2u2, 63V electrolytic C51, C33
10u , 35V electrolytic C37, C22
22u , 35V electrolytic C56, C53, C34, C6, C8, C4, C49, C25, C27, C45, C11,
C46, C36, C10
100u , 25V electrolytic C42
220u , 10V electrolytic C9
1000u , 35V electrolytic C47*, C40*
10u , 35V non polarised elect C23, C29, C31, C57
22u , 35V non polarised elect C1, C2
Non polarised capacitors can sometimes be called bipolar. Unlike ordinary polarised
electrolytic capacitors they can be put into the board any way around.
4

Discrete Semiconductors
BC549 or BC550 Q1-15
1N4002 or 1N4004 D8, D23, D9*, D13*, D14*, D18*, D19*, D24*
1N4148 or 1N914 D1, D2, D3, D4, D5, D6, D11, D12, D15, D16, D17, D20, D21, D22,
D25
BAT-42 D7, D10
LED 3mm green TRIG
LED 3mm red/green L O
LED 3mm red PEAK
LED 3mm yellow ON
The L O LED is a bi-colour LED in a water-clear package. Do not fit an ordinary single
colour LED in this position.
Integrated Circuits
OPA2134PA U1, U7
NE5534 U8
TL072 U3, U5, U6, U9, U16
TL074 U4, U10, U14
7815 U15*
7915 U11*
THAT300P U2
4001 U13
4016 U12
Pots
All pots 16mm Alpha or Alps types.
50K linear dual gang RESONANCE, GAIN
1M log UP, DOWN
50K linear SMOOTH, REQ, IZZ, DRY/WET, THRESHOLD, ENVELOPE
10K linear VOLUME
50K log L O-RATE, L O-DEPTH
Trimmers
22K trimmer TRIM
470K trimmer BAL
5

Switches
SPDT on-on CONT, AUTO, WAVE
SPDT on-off-on MODE
Miscellaneous
Leaded ferrite bead L1
Heatsinks TO-220 clip-on 2 off for U11 and U15
2-way 0.1” KK Molex header 4 off INPUT, SIDE, CV, GATE
3-way 0.1” KK Molex header 1 off OUTPUT
2-way 0.1” KK Molex housing 4 off INPUT, SIDE, CV, GATE
3-way 0.1” KK Molex housing 1 off OUTPUT
16mm Alpha pot brackets 13 off
Off-board Parts
These are fitted to the rear panel
1/4” mono sockets 4 off Input, Side chain input, CV, Gate
1/4” stereo (TRS) socket 1 off Output
Suitable power plug 1 off Power In
I recommend plastic shrouded sockets for both the audio, CV and power sockets. This will
reduce the risk of earth loops.
Additional parts required for stereo operation on both boards
2-way 0.1” KK Molex header 2 off STV, ST-A
2-way 0.1” KK Molex housing 2 off STV, ST-A
4-way 0.156” KK or MTA header 1 off MOTM
4-way 0.156” KK or MTA housing 1 off MOTM
You will also need a power source of some kind. The recommended supply is a wall-wart
supplying 15V AC at 300mA minimum. See later for more information.
A small amount of insulated multistrand wire is needed. This will be used to connect the
sockets and power supply to the board.
IC sockets are to be recommended, especially if this is your first electronics project. You need
eight 8-pin DIL sockets, and six 14-pin DIL sockets. Choose ‘turned pin’ or ‘dual wipe’
types.
6

Circuit Description
Like many complex analogue circuits the iltrex-II issue 2 circuit can be split up in to little
bits. The first bit we will look at is the pre-amplifier stage on page one of the schematic. The
input signal comes in through a small network of passive parts: L1 acts as a filter for radio
frequency interference. C5 and R2 act as a high pass filter removing any DC from the input
signal. R3 and C26 act as a low pass filter removing any unwanted high frequency components
from the input. R3 also protects U1 from possible over voltage.
The pre-amp is built around U1. I have specified the low noise audio op-amp, the OPA2134.
The pre-amplifier is a two stage design. The first stage is a non-inverting amplifier whose
voltage gain can be varied from 1 to 12. C1 keeps the gain for DC and very low frequency
signals at near to one. This prevents any offsets within U1 from being amplified unnecessarily
C3 provides a little bit of high frequency roll-off to keep the amplifier stable.
The second stage of the pre-amp is an inverting amplifier. The GAIN pot is used in a slightly
offbeat way. It is in both the feedback and the input resistors. This way we can control the
gain over a wide range from -0.4 to -10.1. The minus in these numbers shows the inverting
properties of the amplifier.
The voltage gain of the two pre-amplifier stages in tandem can be varied from -0.4 to -122. A
gain of 0.4 means that the output of the pre-amp is only 40% of the input level. While a gain
of 122 means that the output level is 122 times bigger than the input. In audio circles this
would normally defined in dB. This pre-amplifier will give you a gain from -8dB to +42dB.
Because the pre-amplifier is made from a inverting and non-inverting stage, the overall
behaviour is inverting. This means the output is completely out of phase with the input. This is
not a problem since the inversion is corrected later on the iltrex.
Q7 and associating circuitry drive the peak LED. This is designed to light up just as the ladder
filter starts to show heavy distortion.
The main audio path continues on to the filter ladder itself via one half of the resonance pot.
However, the pre-amp also provides the signal for the 'dry/wet' circuit and the envelope
processor. We will deal with these two later.
The filter is based around the traditional ladder as designed originally by Dr. Moog. I have
used THAT300 matched NPN array for the top and bottom pairs in the ladder. This minimises
control current breakthrough to almost zero. Current breakthrough manifests itself as a copy
of the modulating signals on the output. Generally, this is not a good thing. ‘BAL’ biases the
base of the left hand bottom pair (U2, pin 9), via R21, by a small amount to even out any
differences within the ladder. This minimises breakthrough still further.
Two of the rungs of the ladder are ‘sniffed’ by a differential amplifier. Each of these is
identical, based around the classic three op-amp implementation. They are all DC coupled, and
rely on ‘close’ matching to remove any DC offset. A differential amplifier is a device that
makes larger the voltage difference between two points. In our case, the voltage across the
top and bottom filter capacitors. The gain of the differential amplifiers is set higher than
normal ladder filters to improve signal to noise ratio in the following mixer stage. C17 and
7

C18 provide AC coupling of the outputs to remove the slight DC offset from the top
differential amplifier.
The resonance in a moog ladder filter is controlled by the level of audio feedback applied to
the bottom pair of transistors from the output of the differential amplifier at top rung of the
ladder. The level of is typically controlled by the resonance pot, wired as a variable resistor
and a trimming resistor, TRIM. It is traditional to use a 50K reverse log pot for the resonance
control in the classic moog ladder circuit. When set to a value of 50K this pretty much allows
the feedback path to be ignored, and no resonance can be heard. The ‘reverse log law’ is
needed so that as you turn the pot the resonance increases smoothly. An ordinary linear law
pot would do nothing for most of its travel, and then all the resonance would be introduced in
the last quarter of a turn. Not very ‘smooth’ or musical. Unfortunately, 50K reverse log pots
are difficult to find and quite expensive.
In the iltrex-II, we use an 50K linear pot, but we wire it as a potential divider and not as a
variable resistor. The drawback of using a pot on its own like this is that it has a variable
output impedance and the ladder is therefore unbalanced, the degree of which depends on
where the resonance control is set. We get around this by using a buffer on the pot's output.
U3, a unity gain voltage follower, or buffer, 'sniffs' the voltage at the wiper of the resonance
pot and provides a copy at its own output that has a constant impedance.
The resonance pot is a dual gang type too. One gang controls the feedback loop as we have
seen, and the other sets the gain of the input. Normally the passband gain of a moog ladder
decreases as you turn the resonance up. In other words the volume drops as you increase the
resonance. This can be quite a problem for a post processor like the iltrex. So in the iltrex,
the input level is automatically turned up as resonance increases. Thus the overall effect is of a
constant volume at all values of resonance. I thought this was quite clever of me to invent a
way of doing this without increasing noise levels. However, I found out later that the very
same principle was used in the Roland SH-2000 as long ago as 1974.
The other half of U3 acts again as a voltage follower on the wiper of the gain control part of
the resonance pot. This ensures that the ladder's input is fed from a constant resistance no
matter where the resonance pot is positioned.
C11 provides the appropriate decoupling and is sufficiently large so as to allow the filter to
oscillate above 200Hz or so.
our inputs control the filter cut-off frequency via an exponential convertor based around U9.
The filter frequency can be directly controlled with the REQ pot via R63. R65 sets the
sensitivity of the envelope processor’s output. While R67 does the same job for the L O. The
CV input provides a nominal 1V/octave response, and would normally be accessed via a jack
socket on the rear panel.
The exponential convertor is temperature compensated. R61 is the positive temperature
coefficient resistor providing an approximate cancellation of the exponential convertor’s
inherent temperature coefficient.
Note the two pin header, STV, and R60. These allow two iltrex-II modules to be ganged
together to form stereo processing. There is more about this later in the document, but we can
8

see that the output of the CV summing amp is present at pin 1, while a second CV input is
made available at pin 2. The master iltrex-II will be sending the CV signal via pin 1 on the
STV header to pin 2 on the slave's STV header. This way the master iltrex-II board will also
control the slave's cut-off frequency. It would be expected that the connection be done via a
switch so the linking could be turned on or off from the front panel.
The audio path continues from the filter’s differential amplifiers by going on to the mixer
stage. This is shown on page two of the schematics at the top of the page. The mixer stage is
designed to combine the three audio signals created by the iltrex so far: The first and fourth
rung ladder outputs, which will make up the ‘fizz’ and ‘smooth’ outputs respectively. And the
main pre-amplified signal which will go to the 'wet/dry’ balance control.
The two filtered signals go to identical ‘reversible attenuator’ circuits. U5 is wired as two
inverting amplifiers, each with a gain of -1. Each inverted signal is applied to one end of a pot,
while the non inverted signal is applied to the other. By simply moving the wiper of the pot to
one side or the other determines which signal is dominant. When the wiper is in the middle
position the two signals cancel each other out and the voltage is zero. U7a (pins 1, 2, 3) is
configured as an inverting summer. This circuit combines the voltages at each wiper. R38 and
R39 are deliberately low in value when compared to the 50K of the pots. This loads the
relative high impedance output of the pot and warps the law of the pot. This allows the central
null point to be more easily found.
U7b (pins 5, 6,7) in conjunction with the dry/wet pot and R45 form the output balance circuit.
This block allows the user to select between the output of the filter mixer or pre-amplified
signal. It is easy to see how it works when you consider the action of the wiper moving
between one end of its track connected to U7 pin 1 and the other which is connected to the
output of the pre-amplifier.
The output of the mixer stage is fed via a DC blocking capacitor to the ‘Volume’ pot. The
wiper of this is connected to the final output amplifier stage. This is a low noise inverting
amplifier circuit, based around U8, with a gain of -3.7. The op-amp chosen is the 5534 which
is capable of driving larger currents than most ordinary devices. R54 reduces any chance of
high frequency ringing in long cable runs and protects against short circuits. Non polar
capacitor, C57, and R50 remove any small DC offset voltage present on the output of U8.
Now let us look at the little network R48, R51 and C29. This mimics the output impedance of
the main audio output – although the small differences between C29 and C57 and the non zero
output impedance of U8 do not allow it to be an exact match at all frequencies. This network
connects to pin 2 of the output header which goes to the ring of any connected jack plug.
Now if the inserted jack is a mono one the ring terminal will simply be shorted to the sleeve by
the action of the jack plug. Thus the output of the iltrex-II behaves in much the same way as
a traditional unbalanced output. However, if you use a TRS plug (a stereo jack plug but
carrying only a mono signal) then the audio output of the iltrex-II appears as a balanced
impedance output. This can be used as you would a traditional balanced output signal; with
the hot signal being present on the tip, the cold signal on the ring and the ground on the
sleeve.
Many balanced output circuits present the audio signal on both the hot and cold connections;
the signal on the cold connection being an inversion of the signal on the hot. This alone is
9

often considered to be a balanced signal but in truth the receiving end of the balanced
connection cares not for the absolute signal levels on the hot and cold connections but only the
difference between them. And because all balanced input circuits do not have an infinite input
impedance the source impedance is very important to this differencing process. By keeping
both the hot and cold's source impedance as close in value as possible you maximise the ability
of the balanced input's circuitry to reject any unwanted interference on the audio signal.
The advantage over the impedance balanced circuit over the full balanced circuit is two fold:
Simplicity – you have less circuitry in the audio pathway to either go wrong or alter the signal
in some way. And compatibility – the impedance balanced circuit can be used for both
balanced systems and unbalanced systems with no possible problems with stability or short
circuits. Now there are EBOS (electronically balanced outputs stage) circuits around that will
automatically compensate for unbalanced connections but they do add complexity and may be
prone to instability under certain load conditions.
The disadvantage of solely impedance matching is a comparative loss of headroom. The full
balanced system has an additional 6dB of output signal to play with. It is the author's opinion
that this does not make a great deal of difference in the real world.
If the venerable 5534 is replaced by a more modern single op-amp you should remove C28 as
additional compensation will probably not be required. You may also be able to link out the
coupling capacitor, C57 and its twin, C29, if the output offset voltage is negligible. R50 and
R48 may also be removed in this case.
That completes the description of the audio path. Now let us take a look at the processing
circuitry of the iltrex. Staying on page two of the schematics, the second set of circuits down
the page belongs to the full wave rectifier and threshold detector. This takes its input from
wither the pre-amp output or the external side chain input. The choice is determined by the
‘cont’ switch.
The switch's wiper leads straight into some amplification based around U14a. This is an
inverting amplifier with a gain of -3.3. The main pre-amp is expected to produce a maximum
output of around 5Vp-p in normal use, so U14a boosts this signal up to 15Vp-p. The
amplified signal is now full wave rectified by the circuitry based around U14b and associating
circuitry. ull wave rectification can be described by the mathematical ‘absolute’ function. In
other words, the output of the full wave rectifier ( WR) is always positive. If you present
+10V to the input, you will get +10V. But if you present it with -10V you will also get +10V.
Likewise, -5V turns into +5V, -3V into +3V. Now if you put an audio signal into this circuit,
you will get a series of positive bumps that correspond to the up and downs of the audio
signal.
U14d forms a special buffer circuit. This configuration, allows the op-amp to drive medium to
high capacitive loads without instability. We also saw it being used in the output amplifier of
the iltrex. The output of the full wave rectifier is therefore protected by the odd load
presented by the next set of circuits.
Now, no real time system can recover envelope information without some disadvantage of
some sort. Some systems employ the peak and droop method. These are fast to respond to
sudden changes in loudness or envelope. They work by simply charging a capacitor as fast as
10

possible from the WR through a diode. The capacitor is then discharged through a resistor,
sometimes variable but often not, causing the stored voltage to droop at a determined rate.
However, they are often plagued by ripple when used to process certain types of input signal.
Ripple is the bumps from the WR creeping through to affect the required output. This tends
to manifest itself in a ‘buzz’ to the output CV. If you increase the discharge resistor, you can
reduce the bumps but this tends to not allow the CV to drop quick enough when the input
signal ends.
Another method involves low pass filtering of the WR output. This leads to less bumps if the
correct filter cut-off frequency is chosen, but does lead to longer attack times. There are more
complex ways too, involving sample and holds and other clever methods.
In the iltrex the output of the WR is passed to a special circuit called the ‘lag processor’.
This is cleverly combined with the function of the envelope generator and is described in detail
later. At this point I will just say that it functions as a simple low pass filter with controllable
rise and fall times.
But let us stay on page two for now. To create a gate signal we need a very fast response. In
an ideal world this signal must go high the moment the signal arrives and goes low the
moment the signal dies away. In this case I have used the peak and droop method. This does
give us a fast as response as possible, but what about the ripple. Well, ripple is not that
important here. Remember the gate output only goes high or low. What we have to do is
make sure our gate doesn’t ‘rattle’ when it picks up the ripple. In other words, we need our
gate to come cleanly on and off with no spurious states as the signal rises and falls.
U14b (pins 5, 6, 7) is a comparator. This is a device based around an op-amp that determines
whether a signal is higher than a pre-selected threshold voltage. The threshold voltage is
controlled by the user, and is set by the ‘Threshold’ pot. The threshold voltage can be set
between 12V and 0.7V. C44 is charged via D15 from the WR output. D15 allows the
capacitor to be charged up, but not discharged, by the WR’s output. R104 allows the
capacitor’s stored peak voltage to droop at a controlled rate.
Most gate extractors provide a gate signal when the voltage on the capacitor is above a certain
value. The iltrex is similar but once the gate does go high, a certain proportion of the
opamp's high level output is fed back, via D16, to keep the input higher. This forces the
comparator to stay high longer than it would normally do. This allows more ripple to be
present before ‘rattling’ occurs, giving us a cleaner edge to our gates. You don’t have any
control over this amount of positive feedback, it is set by the value of R105. A good
comparator designs have a little positive feedback anyway, it is called hysteresis, and in our
case it is provided by R106. But the additional path via D16 offers a type of one way
hysteresis that gives us better high to low gate transitions.
The comparator’s output is fed via D17 to a transistor Q13. This transistor is turned on when
the comparator’s output goes positive. D17 protects the transistor from damaging negative
output voltages. Q13’s collector will be pulled down to ground when the transistor is turned
on. This in turn controls the envelope generator’s logic circuitry described later.
Lets have a look at the third page and the envelope processor itself. This is quite a hard bit to
understand.
11

The heart of this unit is the circuitry based around U10b (pins 5, 6, 7). This, along with the
‘up’ and ‘down’ pots, make up the lag generator. What is a lag generator? Basically it is a
capacitor, C37 in this circuit, that can discharged and charged at a controlled rate. The level to
which the capacitor charges to, or discharges to, is determined by the input voltage applied to
pin 5 of U10. The voltage across the capacitor will directly control the output of the envelope
processor.
U12 is an analogue switch. It is a good old 4016, and this IC is found in hundreds of synth
circuits. In the iltrex, it doesn’t do a great deal other than select which mode the envelope
processor is going to be in. The 4016 is controlled by the ‘mode’ switch. or the envelope
processor to be in envelope follower, or E , mode, the WR output needs to be patched into
the lag generator. U12 (pins 6, 8, 9) switches on, and U12 (pins 10, 11, 12) is off. The
positive voltage that is being produced by the WR will now start to charge or discharge C37
up and down. The speed of the charging will be controlled by the ‘up’ pot, and the speed of
the discharge will be controlled by the ‘down’ pot. U10c (pins 8, 9, 10) buffers the voltage
across C37 to create the positive going E output signal. U10d (pins 12, 13, 14) inverts this to
produce negative going voltages. The ‘envelope’ pot controls the depth of the effect. The
position of the pot’s wiper will determine the polarity and the level of the final output signal.
D3 and 4, along with R58, create a dead band around zero volts so the pot doesn’t have to be
exactly in the middle for no modulation.
In EG mode, U12 is switched over to allow the output of the EG logic circuity to control the
lag generator. The output of this logic circuitry is either high, +7.5V or low, 0V. The logic
circuitry can operate in two modes, attack-decay (AD) or attack-release (AR).
Several sources can initiate the attack phase. One is the external ‘gate’ signal. This is a switch
type signal that is either at around 0 volts when off, or any positive voltage greater than 3V
when on. The iltrex can easily handle greater voltages, within reason, without damage. D5
protects Q11 from any negative inputs.
Other sources of triggering the attack phase come from the L O and the threshold detector
already discussed in this document. Both of these trigger the unit by pulling the collector of
Q11 down to zero via the TRIG bus.
When a positive gate signal arrives, Q11 turns on and pulls its collector down to ground or
0V. This inverse version of the applied gate signal is sent to two destinations. One is another
transistor, Q14. This is configured as another inverter. Thus the output of Q14 produces a
copy of the gate signal that swings from 0 when off to +15V when on. R86 passes some
current back to the first transistor. This creates a type of Schmitt trigger action which makes
the transistors change state faster. It therefore allows slowly varying signals to trigger the
iltrex. or example you can use a slow sine wave or aftertouch CV to fire the EG.
The output of Q14 is passed on to a CR network that acts as a differentiator. This circuit
produces a positive voltage spike when the gate goes high. The duration of the spike is
determined principally by the values of C43 and R93. D12 prevents a negative spike being
produced when the gate goes low. The positive spike triggers an RS flip-flop circuit based
around two NOR gates, U13.
12

A flip-flop is a sort of a one bit memory, or latch. Once triggered by a positive going pulse at
pin 12, it stays latched. You can only reset it by removing the power or a reset pulse at its
other input, pin 9. When the flip-flop is latched, pin 10 goes high and pin 11 goes low. The
output at pin 10 is passed via R89 and U12 to the lag generator’s input, thus causing C37 to
start to charge upwards. R89 is chosen to interact with R73 to give an input signal of 7.5V in
the high state.
In any mode, removing the gate will reset the flip-flop. The inverted gate signal from Q11
goes to a second differentiator, C39, R92 and D11. When a gate signal is removed, the
positive going edge runs through U13 (pins 1,2,3 & 4,5,6) to reset the flip-flop. Thus
removing a gate signal will cause the lag generator’s output to fall.
Another way to reset the flip-flop is in the AD mode. This utilises the actual output of the lag
generator to control the discharging process. When the output of the lag generator exceeds a
certain value, approximately +3.8V, the flip-flop is reset and the output voltage will drop.
This job is performed by a comparator based around U10a (pins 1, 2, 3) and Q10. The output
of the lag generator is passed onto the comparator by another analogue switch U12 (pins 1, 2,
13). In AR mode, this is switched off and the input to the comparator is held low by R83. In
AD mode, the switch opens to allow the comparator to sniff the output of the lag generator.
When the voltage exceeds +3.8V or so, the comparator’s output goes from 0V to +15V. This
tells the flip-flop that the attack phase is over and the decay phase is about to start. Pin 10
therefore goes low and C37 is discharged via the ‘down’ pot.
R69 and R70 set the +3.8V threshold level. R77 with R78 provides a thin slice of positive
feedback to force the comparator to switch cleanly... it is another Schmitt trigger again.
The L O circuit is quite simple. It is on page two of the schematics.
The first TL072 op-amp, U16a (pins 1, 2, 3) forms part of the integrator. Any positive voltage
applied to the right of R120 will cause the voltage to fall at the output of the op-amp. The
speed at which the voltage falls is controlled by C52 and the size of the voltage applied to
R120. If the applied voltage is negative the op-amp’s output will rise. It is the integrator’s
output that will be used as the source for the triangle wave output.
The second half of the TL072 op-amp is used as a Schmitt trigger. Its output is either high at
+13V, or low at -13V. If the output of the Schmitt is initially low, it requires +6V at the
output of the integrator to make it go high. The integrator will need to produce an output of
-6V to make the Schmitt go low again.
To make any oscillator you normally require an output to be fed back into the input. In a
standard L O like this one, the integrator is fed by the output of the Schmitt trigger. Thus, a
low at the output of the Schmitt causes the integrator to rise. When the integrator’s output
reaches a certain point, the Schmitt switches state and the integrator’s output falls. The
Schmitt trigger changes state once again, and the process repeats itself....
The ‘L O-rate’ pot allows a only a controlled proportional of the Schmitt's output voltage to
reach the integrator. If the proportion is large, the voltage on R120 is large, and the integrator
13

sweeps fast. If the proportion is small, the integrator sweeps slowly. R116 sets the minimum
speed. Don’t be tempted to lower this value any more to get really slow sweeps. Input errors
within the integrator op-amp will take over and your L O won’t oscillate any more.
With C52 at 100n the range of the L O is about 0.05Hz (one cycle in 20 seconds) to 50Hz.
If you make C52 a 220n capacitor the L O will be proportionately slower and you will have
a range of 0.02Hz to 23Hz.
The square wave output is derived from the Schmitt trigger’s output. D25 allows only positive
excursions through. R123 and C55 act as a simple low pass filter to round of the waveforms
edges a little bit. Very fast edges end up as CV breakthrough on the main audio output and are
pretty unpleasant.
The trigger output is simply generated by a transistor, Q12, that turns on when the output of
the Schmitt trigger goes high. The ‘auto’ switch switches the function off by shorting the base
to the emitter when not required.
The last thing to describe is the power supply. This is a standard ‘three terminal regulator'
design straight out of the data book. R96 and C42 provide a decoupled version of +15V for
the logic circuitry. The logic circuitry can generate little spikes on the power supply, that
could get back into the audio if not decoupled properly. R9 and the ‘on’ LED provide power
supply indication. I have put it on the negative supply only to even up the power drains on
both rails.
The iltrex’s power supply can function either with a half wave rectifier for wall warts, or with
full wave for internal transformers. This will covered in more detail later on the document.
14

Audio and Ground Connections
You are going to need five 1/4” jack sockets, four mono and one stereo, to connect your PCB
to the outside world. Each jack is connected to its respective 0.1” headers on the PCB. The
stereo jack socket is to be fitted in the Output position. This is because the audio output of the
iltrex-II is impedance balanced and requires three connections to the outside world. The
stereo one is therefore not being used to carry a stereo signal but a TRS or tip-ring-sleeve
connection. We can use this like we would a true balanced output signal but with full
compatibility with ordinary unbalanced connections too.
The ground pin on each header is always on the right hand side as you look at the board with
the pots facing forwards. This is pin 1 of the header so the ground pin should correspond to
the square pad on the PCB. Each of these pads will be connected to the respective jack
socket’s ground pin, ie. the one that will connect to the barrel of the plug when it is inserted.
On the two pin headers the signal is sent on the furthest left pin of the header, pin 2 on the two
way headers and pin 3 on the three way header.
or each mono socket, it is a good idea to twist the wires together in pairs. Use two different
colours to tell them apart, and try to keep the wiring as short as possible to prevent picking up
hum and other stray fields. You can use screened cable if you wish, and this should be so if
you are using a wooden case to house the iltrex. The screen must go to pin 1 of each 2-way
header as it carries the ground. Pin 1 should thus connect to the socket's sleeve terminal. Pin 2
should connect to the tip terminal of the socket.
or the stereo (TRS) socket you have three connections to make. If you are wanting to use
screened cable you will need to use special balanced cable which comes with a single screen
that overlaps two identical conductors. Like the other connections pin 1 is the ground and
should be connected to any shield if you are using screened cable. As before this should go to
the sleeve lug of the socket. The audio signal is carried from pin 3 of the header and this
should connect to the tip lug of the socket. Pin 2 is the ground compensation input and should
connect to the ring of the output socket.
I recommend that you use plastic sockets and not ones with a metal mounting bush. This
allows any metal case to float electrically with respect to the socket's ground connection.
However, I do recommend you ground your case in a controlled manner as this will reduce the
likelihood of picking up radiated hum fields from other pieces of equipment and wiring. What
we need to do is tie our case to 0V but not tightly. R126 and the 'CASE' solder pad provide an
easy way of doing this.
it a M4 bolt through the rear panel of your metal case. With a washer, spring washer and nut,
fasten a solder tag to it. Solder a piece of insulated wire from the tag to the solder pad 'CASE'
on the PCB. Your case is now grounded.
If you are mounting your PCB to the case via the M3 mounting holes in the top left and top
right of the PCB then you do not need to use the CASE pad. The top right hole, the one next
to the CASE pad, is connected directly to the CASE pad. By simply bolting the board to your
case with metal hardware you will ensure your case is adequately grounded.
15

If you have used metal sockets then you don't need to ground your case via the 'CASE' pad
since your case will be grounded very tightly via all the sockets. However, this may cause
earth loop problems if you then mount your case into a rack with other pieces of equipment in
it.
Please note that grounding a case is not the same as earthing a case. Your case must be
additionally earthed if you are fitting an internal mains transformer into your case. Please see
the next section for some more details on this.
16

Power Supply and Power Supply Connections
The recommended option is to use an insulated plugtop (often called a wallwart) AC adapter.
They are used external to the iltrex housing and plug into the iltrex using the two pole
barrel connector. They are very safe since all the dangerous high voltage stuff is kept inside
the wall-wart.
You need a 15V or 18V alternating current (AC) output at 250mA or higher rating. Do not
use a DC output type. Although the latter are the most common type of wallwart for guitar
effects pedals, they will not work with the iltrex. To reiterate, because this is really
important, it must say 15VAC or 18VAC on it somewhere.
inding such a power supply is not always as easy as it should be. So many plugtop supplies
these days are switch mode DC output types. However, unregulated AC output ones are out
there and most decent electronic parts suppliers will have them, as well as online guitar effects
shops and even some music shops. Since a wallwart supply will have its own mains plug built
into the case it's not practical for me to list an example for every country out there. In addition
listing a part number for a generic power supply is a bit like a game of whack-a-mole as the
moment I give the part number that very part will disappear and a new one with a different
part number will appear. If you do get stuck it may be best to ask on the forum and see what
other members suggest. That said if you are in the UK and have a arnell account you could
try their part number: 2368009.
Some 12V AC output types may also work but this is only because some AC output wallwarts
tend to be poorly regulated and have a lot of overhead. Do be aware that if they do work
some of the time they may not work all of the time. If the voltage does fall below the required
operating voltage of the iltrex-II the most obvious sign is an audible hum from the outputs.
You will not damage the iltrex-II by doing this although any connected amplifier or speaker
system may object to the humming.
To connect your wall wart to the iltrex you need a suitable chassis mounting connector. You
must ensure you get one that has a plastic housing and plastic mounting bush. This means that
there should be no electrical contact between the case and the power socket. Do not get one
that has a metal mounting bush as this will inevitably connect one of the AC connections
directly to the case.
Make sure too that you get the right socket for the plug you have on the wall wart. Some wall
warts give you a little bundle of different types to choose from. Ensure that the socket you get
allows the plug to slip in easily yet not break connection when wiggled gently. If you are
making up your own plug for it, since it is AC, it does not matter which wire goes to what.
There is no + or -.
Once fitted to your case the socket must then be connected to the PCB. One terminal goes to
AC1 and the other goes to AC2 on the PCB. If your wires are longer than 100mm or so then
it is a good idea to twist them together. This reduces the amount of radiated noise from the
wiring.
AC3 and AC0 are left unconnected.
17

Internal Mains Transformer
The following advice is only for those who know how to wire mains rated equipment safely. If
you do not know how to do this then make no attempt to do so. I do not endorse this method
of powering any Oakley equipment. It is up to you to use your PCB wisely. I take absolutely
no responsibility for your actions with this board. I will offer no further advice than what you
see here in italics:
Transformer rating: Secondaries: 18-0-18 @ 250mA or 18-0, 18-0 @ approx 15VA tota
Connect common, or centre tap, to AC1 and/or AC0. Others to AC2 and AC3.
Line fuse: T250mA
Any meta case must be earthed direct y from the mains in et socket with a thick piece of wire
and suitab e bonding point on the case.
0V on the board shou d a so be tied to earth using a piece of wire connecting the earth
bonding point and the 'CASE' so der pad on the board. R126 shou d be a wire ink and not a
resistor.
Powering the Filtrex with the MOTM header
The iltrex may also be powered from the MOTM or Oakley power busses. The power socket
is 0.156” Molex/MTA 4-way header is marked as MOTM on the PCB. riction lock types are
recommended. The pin out is as follows:
Power Pin number
+15V 1
Module GND 2
Module GND 3
15V 4
Pin one is depicted by the diagonal on the legending. If you are using the MOTM system to
power your iltrex, be sure not to fit the following components which make up the iltrex's
own +/-15V regulated supply:
U15, U11, D13, D14, D18, D19, D9, D24, C40, C47, C38, C50
You can also use the iltrex to power other MOTM/Oakley modules using the MOTM
header. However, be sure not to exceed the power rating of the wallwart, transformer,
heatsinks and smoothing capacitors.
18

Trimmers
TRIM: Adjust this trimmer so that the filter bursts into oscillation when the ‘resonance’ pot is
moved close to its maximum setting. The filter should oscillate from about 100Hz to over the
range of your hearing. Or you can adjust it so that it never goes into oscillation at all. This will
prevent you from accidentally damaging your ears, your tweeters and upsetting your
neighbour’s dogs. But hey, that would be boring. Live life in the fast lane. Trim it up so that it
just oscillates when the resonance it up full.
BAL: Listen to the ‘Smooth’ output. Set the Resonance and requency pots to their mid
positions. Turn the L O modulation depth pot to its maximum value and select the triangle
wave. Adjust BAL until the clicking or buzzing becomes minimised.
19

Housing your unit
The PCB has been designed to fit into a standard 1U high 19” rack unit. Your local parts
distributor will probably have these. Good rack units are quite expensive, and will contribute
heavily to the final cost of your completed iltrex. Expect to pay around 35GBP or so.
In the UK the ones I recommend are made by Bryant Broadcasting or Holt Broadcasting
Services. You can use the Schaeffer rontplatten database provided on the project webpage as
a template for any drilling of holes in the front panel.
The Bryant and Holt ones are superbly made, but they do not allow you to use a 3mm thick
Schaeffer front panel in place of their own. Their cases actually utilise the front panel as part
of the enclosure. Simply swapping the Bryant or Holt panel with one obtained from Schaeffer
will not work as the case would no longer be able to held together. Bryant and Holt do
custom metal work, so it may be possible to try their services. This is one area I would like to
try in the near future.
Schaeffer, and their US franchise ront Panel Express, are also able to engrave panels that are
sent to them. One could send them the blank Bryant panel and they could engrave this with the
rontplatten database found on the iltrex website. I have heard from one person who has
tried this and he was very pleased with the result. Remember if you do decide to do this, you
must remove the four mounting holes from the rontplatten database before sending it to
Schaeffer or ront Panel Express as these are already present on the Bryant panel. I am not
sure whether this could be successfully done with the grey painted finish of the Holt panels.
A Schaeffer PD file can be found on the iltrex's project webpage which can be downloaded
and edited. If printed out at 100% size and in 'wire mode' with reference points, you can then
use it as a template for drilling your own front panel holes.
My current favourite method of labelling a front panel on one of these empty rack cases is to
use a thin (1.5mm) engraved black anodised aluminium 'overlay' panel from Schaeffer. This is
held onto the main case's front panel by three or more 3mm screws at suitable points along
overlay and the components simply stick out the holes in the overlay. The pot nuts are secured
to the front panel of the rack case which hold the board in place. Once the PCB is fitted and
tested the overlay can then be secured into place. The pot holes in the overlay will need to be
sufficiently large enough not to snag on the pot nuts and washers and the PD should be
edited accordingly. I use 14mm diameter holes in the overlay which are big enough to not foul
the pot nuts but are small enough to be nicely covered up by the control knobs. The LED
holes need to be 3.2mm and the switch hole 7mm.
If you buy the rack cases made by Vero, you will find that the height of the unit internally is
quite restricting. The bottom and lower panels have 6mm folds in them at the front. This
affects the amount of space available for the pots and circuit board at the front panel. It is
possible to use these cases as I have done in the past but you will need to mount the board
high enough on the front panel to prevent the pot pins shorting with the case.
20