Tektronix 543B User manual
WARRANTY
All
Tektronix
instruments
are
warranted
against
defective
materials
and
workman
ship
for
one
year,
Tektronix
transformers,
manufactured
in
our
own
plant,
are
war
ranted
for
the
life
of
the
instrument.
Any
questions
with
respect
to
the
war
ranty
mentioned
above
should
be
taken
up
with
your
Tektronix
Field
Engineer.
Tektronix
repair
and
replacement-part
service
is
geared
directly
to
the
field,
there
fore
all
requests
for
repairs
and
replace
ment
parts
should
be
directed
to
the
Tek
tronix
Field
Office
or
Representative
in
your
area.
This
procedure
will
assure
you
the
fastest
possible
service.
Please
include
the
instrument
Type
and
Serial
number
with
all
requests
for
parts
or
service.
Specifications
and
price
change
priv
ileges
reserved.
Copyright
©
196
by
Tektronix,
Inc.,
Beaverton,
Oregon.
Printed
in
the
United
States
of
America.
Ail
rights
reserved.
Contents
of
this
publication
may
not
be
re
produced
in
any
form
without
permission
of
the
copyright
owner.
CONTENTS
Warranty
Section
1
Characteristics
Section
2
Operating
Instructions
Section
3
Circuit
Description
Section
Maintenance
Section
5
Calibration
Section
6
Parts
List
and
Diagrams
A
list
of
abbreviations
and
symbols
used
in
this
manual
will
be
found
on
page
6-1.
Change
information,
if
any,
is
located
at
the
rear
of
the
manual.
The
Type
543B
Oscilloscope
SECTION
1
CHARACTERISTICS
Introduction
The
Type
5 3B
Oscilloscope
is
a
versatile
laboratory
instrument
designed
for
use
with
all
Tektronix
lettered-
or
1
-series
plug-in
units.
VERTICAL
DEFLECTION
SYSTEM
Refer
to
Table
1-1
for
the
characteristics.
Trigger
Source
Selection
Trigger
Mode
Selection
Trigger
Signal
Requirements
SWEEP
GENERATOR
Sweep
Rates
0.1
µsec/cm
to
5
sec/cm
in
2
calibrated
steps.
Displayed
sweep-r
a
te
accuracy
is
±
3%.
An
unc
a
libraied
variable
sweep
rate
control
permits
the
sweep
to
be
slowed
to
at
least
0.
of
the
indicated
rate.
Sweep
Magnification
Any
sweep
rate
can
be
increased
2,
5,
10,
20,
50
or
100
times
by
expanding
the
center
portion
of
the
display
horizontally.
Sweep-rate
accuracy
is
within
~5%
in
the
magnified
positions
until
the
sweep
rate
exceeds
0.02
µsec/cm.
Internal,
external,
and
fine.
Automatic,
d
c
,
ac,
and
ac
low-frequency
rejection.
Internal
(ac):
Minimum
deflection
is
2
mm,
from
150
cps
to
10
m
c
,
rising
to
1
cm
at
30
me
with
less
than
1
mm
of
horizontal
jitter
at
a
sweep
rate
of
20
nsec/cm.
Internal
(de):
Minimum
deflection
is
6
mm
to
10
m
c
.
Internal
(ac
low-frequency
rejection):
Mini
mum
deflection
is
2
mm,
from
30
kc
to
10
m
c
,
rising
to
1
cm
at
30
m
c
with
less
than
1
mm
of
horizontal
jitter
at
a
sweep
rate
of
20
nsec/cm.
Internal
(automatic):
5
mm
deflection
at
150
cps.
Will
trigger
from
50
cps
to
10
m
c
with
increased
deflection.
External
(ac):
Minimum
amplitude
is
0.2
volt,
from
150
cps
to
10
m
c
,
rising
to
1
volt
at
30
m
c
with
less
thon
1
mm
of
hori
zontal
jitter
at
a
sweep
rate
of
20
nsec/cm.
Plug-In
Characteristics
for
the
Ty e
543B
Oscillosco e
TABLE
1-1
Plug-In
Unit
Calibrated
Deflection
Factor
Minimum
Bandpass
Risetime
Input
Capacitance
Type
1A1*
50
mv/cm
to
20
v/cm
5
mv/cm
dc
to
33
m
c
d
c
to
23
m
c
10.6
nsec
15.2
nsec
15
pf
Type
1A2*
50
mv/cm
to
20
v/cm
d
c
to
33
m
c
10.6
nsec
15
pf
Type
B
0.005
v/cm
to
20
v/cm
0.05
v/cm
to
20
v/cm
2
cps
to
12
m
c
d
c
to
20
m
c
30
nsec
18
nsec
7
pf
Type
CA*
0.05
v/cm
to
20
v/cm
d
c
io
2
m
c
15
nsec
20
pf
Type
D
1
mv/cm
to
50
v/cm
d
c
to
300
kc-2
m
c
0.18
,u.sec
7
pf
Type
E
50
v/cm
to
10
mv/cm
0.06
cps
to
20
kc-
60
kc
6
/xsec
50
pf
Type
G
0.05
v/cm
to
20
v/cm
d
c
to
20
m
c
18
nsec
7
pf
Type
H
5
mv/cm
to
20
v/cm
d
c
to
15
m
c
23
nsec
7
pf
Type
K
0.05
v/cm
to
20
v/cm
d
c
to
30
m
c
12
nsec
20
pf
Type
L
5
mv/cm
to
2
v/cm
0.05
v/cm
to
20
v/cm
3
cps
to
2
m
c
d
c
to
30
m
c
15
nsec
12
nsec
20
pf
Type
M*
0.02
v/cm
to
10
v/cm
d
c
to
20
m
c
17
nsec
7
pf
Type
N**
10
mv/cm
ac
to
600
m
c
0.6
nsec
50
input
Z
Type
O
x
*
0.05
v/cm
to
20
v/cm
d
c
to
25
m
c
1
nsec
7
pf
Type
Q**
10
Strain/cm
to
10,000
Strain/cm
d
c
to
6
kc
60
«sec
Adjustable
Type
R**
0.5
ma/cm
to
100
ma/cm
Type
S**
0.05
v/cm
to
0.5
v/cm
Type
Z**
0.05
v/cm
to
25
v/cm
d
c
to
13
m
c
27
nsec
2
pf
*
Multiple-trace
plug-in
units.
**
Special
feature
plug-in
units.
See
your
Tektronix
catalog
for
more
information
on
any
of
these
plug-in
units.
1-1
Characteristics
—
Ty e
543B/RM543B
External
(ac
low-frequency
rejection):
Mini
mum
deflection
is
0.2
volt
from
30
kc
to
10
m
c
,
rising
to
1
volt
at
30
m
c
with
less
than
1
mm
of
horizontal
jitter
at
a
sweep
rate
of
20
nsec/cm.
External
(d
c
):
Minimum
amplitude
is
0.2
volt
to
10
m
c
,
rising
to
1
volt
at
30
m
c
with
less
than
1
mm
of
horizontal
jitter
at
a
sweep
rate
of
20nsec/cm.
External
(automatic):
0.5
v
ot
150
cps.
Will
trigger
from
50
cps
to
10
m
c
with
increased
signal.
Accelerating
10
kv.
Potential
Usable
Viewing
Area
Focus
6-cm
high
by
10-cm
wide.
Vertical:
2
horizontal
lines/mm
distinguish
able
over
the
center
cm.
1.5
horizontal
lines/mm
distinguishable
in
the
top
and
bottom
1
cm.
HORIZONTAL
DEFLECTION
SYSTEM
The
following
characteristics
apply
when
the
HORIZONTAL
DISPLAY
switch
is
set
to
the
EXT
position.
Phosphor
Graticule
Deflection
Factor
A
calibrated
deflection
of
0.1,
1
or
10
volts/cm
with
the
VARIABLE
10-1
control
set
fully
clockwise.
The
VARIABLE
10-1
control
provides
at
least
a
10:1
attenua
tion
of
the
input
signal
when
it
is
turned
Frequency
Response
Input
Characteristics
fully
counterclockwise.
D
c
to
500
kc
at
maximum
gain
(30%
down).
1
megohm
paralleled
by
approximately
3
pf.
AMPLITUDE
CALIBRATOR
Output
Voltage
0.2
mvolts
to
100
volts
peak-to-peak
in
18
steps.
Frequency
Approximately
a
1-kc
square
wave.
Amplitude
Accuracy
Peak-to-peak
amplitude
accuracy
is
±3%
of
indicated
value.
The
special
output
from
the
.1
V
I
NTO
50
connector
is
accurate
to
within
±3%
of
the
indicated
value.
Horizontal:
2
time
markers./mm
distinguish
able
over
the
middle
8
cm.
1.5
time
markers/mm
distinguishable
in
the
first
and
tenth
cm.
Type
31
phosphor
is
normally
supplied.
Other
phosphors
are
available.
6
X
10
cm
with
vertical
and
horizontal
1-cm
divisions
with
2-mm
markings
on
the
centerlines.
Markings
for
measuring
rise
time
have
been
provided
a
t
the
2.5
cm
points
above
and
below
the
graticule
center
line.
Line
Voltage
Line
Frequency
Power
Consumption
POWER
SUPPLIES
108,
115,
122,
216,
230
or
2
volts.
Will
regulate
within
±10%
of
design-center
voltage.
50
to
60
and
00
cps.*
535
wa
t
ts
maximum.
“
ith
a
line
frequency
of
400
cycles,
a
special
fan
modification
is
required;
contact
your
local
Tektronix
Field
Representative.
MECHANICAL
Construction
Net
Weight
Front
panel
is
anodized.
Chassis
is
alumi
num
alloy.
81
pounds.
FRONT-PANEL
OUTPUT
SIGNALS
SAWTOOTH
OUT
Approximately
a
130-volt,
peak-to-peak
sawtooth
voltage
having
the
same
dura
tion
as
the
sweep.
Minimum
allowable
load
resistance
is
100
k.
-GATE
OUT
Approximately
a
20-volt
peak-to-peak
square-wave
pulse
having
the
same
dura
tion
as
the
sweep.
Minimum
dc
load
resis
tance
is
5
k.
VERT
SIG
OUT
Vertical
signal
output
connector.
Output
amplitude
is
at
least
1.2
vo
l
ts/cm
of
de
flection
on
the
crt.
Output
is
ac
coupled.
CATHODE-RAY
TUBE
Type
T5 70-31-2.
Unblanking
De
coupled.
ACCESSORIES
INCLUDED
Tektronix
Part
No.
2
Instruction
Manuals
070- 37
2
P6006
Probes
with
BNC
connectors
010-127
2
Adapters,
BNC
to
Binding
Post
103-033
1
Test
Lead
012-031
1
Crt
Protector
Plate
387-918
1
50-ohm
Cable,
BNC
to
BNC,
18
inches
long
012-076
1
3-wire
Power
Cord
161-010
1
3-
to
2-wire
Adapter
103-013
1
Adapter,
BNC
to
UHF
103-015
12
10-2
x
5
/
16
THS
Screws
212-533
12
10-32
x
5
/
16
THS
Screws
212-535
1-2
SECTION
2
OPERATING
INSTRUCTIONS
FUNCTION
OF
CONTROLS
AND
CONNECTORS
HORIZONTAL
DISPLAY
Selects
the
amplitude
point
on
the
trigger
ing
signal
where
sweep-triggering
occurs.
Adjusts
the
oscilloscope
for
a
stable
dis
played
waveform.
The
STABILITY
corrrol
can
be
set
to
the
PRESET
position
and
left
there.
This
position
provides
for
con
venient
triggering
since
only
the
TRIGGER
ING
LEVEL
control
needs
to
be
adjusted
to
obtain
a
stable
display.
TRIGGERING
MODE
AUTO:
Permits
normal
triggering
or
simple
waveforms
with
repetition
rates
higher
than
about
50
cps.
With
no
trigger
signai,
or
with
a
lower
repetition
rate,
the
trigger
circuit
free
runs
at
approximately
0
cps
and
triggers
t
he
time
base
at
this
rate,
pro
providing
a
reference
trace.
MAGNIFIER
Lamps
AC
LF
REJ:
Attenuates
trigger-signal
fre
quencies
below
about
17
kc,
allowing
the
trigger
circuit
to
respond
only
to
higher
frequencies.
AC:
Blocks
the
dc
component
of
the
trig
gering
signal
and
allows
triggering
to
take
place
only
on
the
changing
portion
of
the
signal.
With
frequencies
below
about
30
cps,
use
the
DC
position.
EXTERNAL
HORIZONTAL
VOLTS
/CM
VARIABLE
SINGLE
SWEEP
For
best
triggering
at
high
frequencies,
use
an
ac
coupling
position
of
the
TRIG
GERING
MODE
switch.
DC:
Permits
triggering
on
both
high-
and
low-frequency
(to
d
c
)
signals.
TRIGGER
SLOPE
Determines
whether
the
time
base
is
trig
gered
on
the
negative-
{
—
)
or
positive-
(+)
going
slope
of
the
signal.
LINE:
Uses
a
line-frequency
signal
as
a
trigger.
INT:
Uses
a
portion
of
the
signal
applied
to
the
vertical
deflection
plates
of
the
c
rt
as
a
trigger
signal.
EXT:
Provides
external
triggering
on
a
signal
applied
to
the
TRIGGER
INPUT
connector.
TIME,/CM
Selects
the
time-base
sweep
rate.
READY
Lamp
HORIZONTAL
POSITION
and
VERNIER
AMPLITUDE
CALIBRATOR
POWER
ON
INTENSITY
FOCUS
ASTIGMATISM
TIME/CM
VARIABLE
Provides
an
uncalibrated
sweep
rate
ad
justment.
The
sweep
rate
can
be
slowed
to
at
least
0.
X
any
setting
of
the
TIME/
CM
switch.
An
UNCALIBRATED
lamp
lights
when
the
VARIABLE
control
is
not
in
the
CALIBRATED
position.
TRACE
ROTATION
NORMAL
(X
1
)
and
SWEEP
MAGNIFIED
positions
expand
the
display
horizontally
by
the
amount
indicated.
Sweep-rate
ac
curacy
is
±:5%
in
the
magnified
posi
tions.
EXT
position
allows
an
external
signal
to
drive
the
horizontal
deflection
system.
The
horizontal
deflection
factor
is
set
by
the
EXTERNAL
HORIZONTAL
VOLTS/CM
switch
and
variable.
The
MAGNIFIER
ON
lamp
lights
when
ever
the
HORIZONTAL
DISPLAY
switch
is
in
any
of
the
SWEEP
MAGNIFIED
posi
tions.
The
MAGNIFIER
UNCALIBRATED
lamp
is
connected
to
light
whenver
the
sweep
rate
exceeds
the
maximum
cali
brated
rate
of
0.02
usec/cm.
This
lamp
will
not
light
as
long
as
the
setting
of
the
TIME/CM
switch,
divided
by
the
mag
nification
factor
is
not
faster
than
0.02
se
c
.
Selects
the
horizontal
deflection
factor
when
the
HORIZONTAL
DISPLAY
switch
is
set
to
EXT.
The
VARIABLE
control
must
be
fully
clockwise
when
using
the
cali
brated
horizontal
deflection
factors.
Permits
single
sweep
operation
at
ail
settings
of
the
HORIZONTAL
DISPLAY
switch
except
EXT.
Lights
when
time-base
circuit
is
ready
for
triggering
after
being
reset.
Positions
the
display
along
he
horizontal
axis
of
the
crt
.
Determines
the
peak-to-peak
voltage
avail
able
at
the
CAL
OUT
connector.
Toggle
switch
for
turning
the
instrument
power
on
and
off.
Controls
brightness
of
the
display.
Used
in
conjunction
with
the
INTENSITY
and
ASTIGMATISM
controls
for
obtaining
a
well-defined
display.
Used
in
conjunction
with
the
INTENSITY
and
FOCUS
controls
for
obtaining
a
well-
defined
display.
Permits
horizontal
alignment
of
the
trace
with
respect
to
the
horizontal
lines
of
the
graticule.
The
TRACE
ROTATION
con
trol
is
a
screwdriver
adjustment
concentric
with
the
ASTIGMATISM
control.
®L
2-1
TRIGGERING
LEVEL
STABILITY
O erating
Instructions
—
Ty e
543B/RM543B
SCALE
ILLUM
Varies
illumination
of
the
graticule
grid
lines.
Beam
Position
Four
neon
lamps
with
accompanying
arrows
indicate
the
direction
when
the
display
is
deflected
out
of
the
viewing
area.
TRIGGER
INPUT
Connector
for
applying
an
external
trigger
signal
to
the
time
base
when
TRIGGER
SLOPE
switch
is
set
to
the
EXT
position.
+
GATE
OUT
Supplies
approximately
a
20-volt
square
wave
pulse
when
the
time
base
is
oper-
a'ing.
Pulse
dur
a
tion
is
approximately
10.
5X
the
setting
of
the
TIME/CM
switch.
NORMAL
SWEEP
Power
Connections
Unless
otherwise
indicated,
the
Type
5 3B
is
shipped
with
rhe
power
transformer
and
fan
wired
for
1
15-volt
ac
input.
A
connection
diagram
on
the
side
of
the
trans
former
and
Fig.
2-1
shows
alternative
connections
for
other
input
voltages
to
the
power
transformer.
When
the
trans
former
is
changed
from
a
108,
115,
or
122
volts
to
216,
230,
or
2
volts
connection,
the
fan
wiring
must
be
changed.
Fig.
2-2
shows
the
fan
connections
for
each
voltage
range.
SAWTOOTH
OUTSupplies
the
sawtooth
voltage
of
the
time
base.
Peak
amplitude
is
about
—
130
volts.
EXTERNAL
HORIZ
INPUT
Jack
for
applyin
g
external
horizontal
sig
nal
when
the
'HORIZONTAL
DISPLAY
switch
is
set
to
EXT.
VERT
SIG
OUT
CRT
CATHODE
SELECTOR
(rear
panel)
EXTERNAL
CRT
CATHODE
Vertical
signal
output
connector.
Output
amplitude
is
approximately
1.2
volts/cm
of
deflection.
Provides
blanking
of
between-channe!
switching
transients
(in
the
CHOPPED
BLANKING
position)
when
using
multi
channel
plug-in
units
in
the
chopped
mode.
With
the
ground
strap
disconnected,
this
connector
applies
Z-axis
modulation
sig
nals
to
the
crt
cathode.
The
Z-axis
signa's
should
be
at
leas
’
20
volts
in
amplitude
to
cause
intensity
modulation.
Always
have
the
ground
strap
connected
except
when
applying
Z-axis
modulating
signals.
Fig.
2-2.
Fan
connections
for
100-124
volts
and
220-248
volts.
See
the
label
on
the
side
of
T601
for
the
placement
of
jumper
leads.
Fig.
2-1.
Transformer
connections
for
108
to
244
volt,
50
Io
60
cps
and
400
cps
operation.
Sweep
Triggering
Proper
sweep
triggering
is
essentia'
for
a
stable
presenta
tion
of
an
input
signal.
For
a
stable
display,
the
sweep
must
be
triggered
at
the
same
time
relative
to
the
displayed
signal.
Thus,
the
sweep
must
be
triggered
by
the
input
signal
or
by
some
external
signal
that
has
a
fixed
time
relationship
with
the
displayed
signal.
The
external
trigger
signal
must
be
the
same
frequency
or
a
multiple
of
the
input
signal.
Selecting
the
Trigger
Source
The
TRIGGER
SLOPE
switch
selects
one
of
a
variety
of
possible
triggering
signcis.
For
most
applications,
T
he
sweep
can
be
triggered
internally
from
the
clisp
ayed
signal.
This
occurs
with
the
TRIGGER-SLOPE
switch
set
at
either
+
or
-
INT.
The
LINE
positions
of
the
TRIGGER
SLOPE
switch
connect
a
line-frequency
signal
to
the
triggering
input.
Line
trigger
ing
is
useful
whenever
the
input
signal
is
frequency-related
to
the
line
frequency.
To
trigger
the
t
i
me
base
from
an
external
signal,
set
the
TRIGGER
SLOPE
switch
to
an
EXT
position
and
connect
the
2-2
O erating
Instructions
—
Ty e
543B/RM543B
TRIGGER
SLOPE
TRIGGER
SLOPE
Fig.
2-3.
Effects
of
the
TRIGGERING
LEVEL
ond
SLOPE
controls.
2-3
O erating
Instructions
—
Ty e
543B/RM543B
trigger
signal
to
the
TRIGGER
INPUT
connector.
External
triggering
is
often
used
when
signal
tracing
in
amplifiers,
phase-shift
networks,
and
wave-shaping
circuits.
The
signal
from
a
single
point
in
the
circuit
can
be
used
as
an
external
trigger
signal.
With
this
arrangement,
it
is
possible
to
observe
the
polarity,
shaping
and/or
amplification
of
a
signal
at
various
points
through
the
circuit
without
resetting
the
triggering
controls
for
each
new
display.
Selecting
Triggering
Mode
Four
means
of
trigger
coupling
are
available
with
the
TRIGGERING
MODE
switch.
The
different
coupling
posi
tions
permit
you
to
accept
or
reject
certain
frequency
com
ponents
of
the
triggering
signal.
With
the
switch
set
at
AC,
the
time
base
can
be
triggered
with
all
frequency
components
of
the
triggering
signal
within
the
trigger
amplifier
bandpass,
including
dc
levels.
With
the
switch
set
at
AC
LF
REJ,
dc
and
low-frequency
signals
(below
about
17
kc)
arc
rejected
or
attenuated.
Thus,
the
trigger
circuit
will
respond
best
to
the
higher-frequency
components
of
the
triggering
signal.
With
the
switch
set
to
AUTO,
proper
triggering
auto
matically
takes
place
providing
that
rhe
signal
waveform
is
comparatively
simple
and
approximately
symmetrical.
With
no
trigger
signal,
or
with
a
lower
repetition
rate,
the
trigger
circuit
free
runs
at
approximately
40
cps
and
triggers
the
time
base
at
this
rate,
providing
a
reference
trace.
In
general,
use
AC
coupling.
However,
it
will
be
necessary
to
use
DC
coupling
for
very
low-frequency
signals.
When
line-frequency
hum
is
mixed
with
the
triggering
signal,
it
is
best
to
use
AC
LF
REJ
coupling
so
that
triggering
takes
place
only
on
the
signa!
of
interest
(if
the
signal
of
interest
contains
frequency
components
above
about
17
kc).
The
AC
LF
REJ
position
is
also
useful
when
triggering
internally
from
multitrace
plug-in
units
operated
in
the
alternate
dual-trace
mode.
AC
LF
REJ
coupling
has
a
faster
recovery
time
when
subjected
to
the
alternate
d
c
levels
from
the
multitrace
plug-in
unit.
Selecting
Trigger
Slope
The
TRIGGER
SLOPE
switch
determines
whether
the
trigger
ing
circuit
responds
on
the
rising
(
+
setting)
or
the
falling
(
—
setting)
portion
of
the
triggering
signal.
When
several
cycles
of
a
signal
appear
in
the
display,
the
setting
of
the
TRIGGER
SLOPE
switch
will
probably
be
unimportant.
How
ever,
if
you
wish
to
look
at
only
a
certain
portion
of
a
cycle,
the
TRIGGER
SLOPE
switch
will
help
start
the
display
on
the
desired
slope
of
the
input
signal.
Fig.
2-3
illustrates
the
effect
of
both
the
TRIGGER
SLOPE
and
TRIGGERING
LEVEL
controls.
Setting
Stability
Control
In
nearly
all
triggering
applications,
satisfactory
opera
tion
can
be
obtained
with
the
STABILITY
control
in
the
PRESET
(fully
counterclockwise)
position.
The
PRESET
posi
tion
has
the
advantage
of
requiring
no
further
adjustment
of
the
STABILITY
control
when
switching
from
one
triggering
signal
to
another.
However,
if
stable
triggering
becomes
difficult
with
the
STABILITY
control
at
PRESET,
it
will
be
necessary
to
adjust
the
control
for
proper
triggering.
To
adjust
the
STABILITY
control,
place
the
TRIGGERING
LEVEL
control
in
the
fully
counterclockwise
position,
then
turn
the
STABILITY
control
slowly
clockwise
until
a
trace
appears
on
the
crt.
The
correct
setting
is
obtained
by
turning
the
control
counterclockwise
three
to
five
degrees
from
the
point
where
the
trace
appears.
Setting
Triggering
Level
The
TRIGGERING
LEVEL
control
determines
the
amplitude
point
on
the
signal
where
triggering
occurs.
The
trigger
circuit
is
most
sensitive
to
ac
triggering
signals
with
the
TRIGGERING
LEVEL
control
set
near
zero.
Moving
the
TRIGGERING
LEVEL
control
in
the
+
(plus)
direction
causes
the
trigger
circuit
to
respond
at
some
higher
positive
amplitude
on
rhe
triggering
signal.
Moving
the
TRIGGERING
LEVEL
control
in
the
—
(minus)
direction
causes
the
trigger
circuit
to
respond
at
some
higher
negative
amplitude
on
the
triggering
signal.
Selecting
Time/Cm
(Sweep
Rate)
The
TIME/CM
and
HORIZONTAL
DISPLAY
switches
con
trol
sweep
rate.
The
TIME/CM
and
HORIZONTAL
DISPLAY
switches
allow
you
to
view
an
applied
signal
at
a
wide
variety
of
cali
brated
sweep
rates.
When
making
time
measurements
from
the
crt,
be
sure
the
VARIABLE
control
is
set
to
CALIBRATED.
When
the
HORIZONTAL
DISPLAY
switch
is
set
to
NORMAL
(X
1
),
the
TIME/CM
switch
indicates
the
true
sweep
rate.
However,
with
the
HORIZONTAL
DISPLAY
switch
set
to
a
sweep
magnified
position,
the
setting
of
the
TIME/CM
switch
must
be
divided
by
the
magnified
amount
to
determine
the
true
sweep
rate.
For
example,
assume
that
the
TIME/CM
switch
is
set
at
1
mSEC
and
the
HORI
ZONTAL
DISPLAY
switch
is
set
to
X5.
In
this
case,
the
true
sweep
rate
would
be
1
(msec)
divided
by
5
(magnified
amount);
resulting
in
a
displayed
sweep
ra
t
e
of
0.2
msec/
div.
Fig.
2-
illustrates
how
to
make
time
measurements
from
the
graticule.
2-
O erating
Instructions
—
Ty e
543B/RM543B
Single-Sweep
Operation
In
applications
where
the
displayed
signal
is
not
repeti-
tive
or
varies
in
amplitude,
shape,
or
time,
a
photograph
of
a
conventional
repetitive
display
may
produce
a
jumbled
presentation.
To
avoid
this,
use
the
single-sweep
feature
to
photograph
this
type
of
display.
To
use
single
sweep,
first
make
sure
the
trigger
circuit
will
trigger
on
the
event
you
wish
to
display.
Do
this
in
the
conventional
manner.
Then,
press
the
SINGLE
SWEEP
switch
to
RESET
and
release.
When
this
is
completed,
the
next
trigger
pulse
will
actu
at
e
the
sweep
and
the
Type
5 3B
will
display
the
event
on
a
single
trace.
The
READY
lamp,
near
the
SINGLE
SWEEP
s
wit
ch,
first
lights
when
the
sweep
is
ready
to
a
ccept
a
trigger
and
then
goes
out
after
triggering
has
taken
place.
To
ready
the
circuit
for
another
single
display,
press
the
SINGLE
SWEEP
switch
to
RESET
and
release.
In
single
sweep
operation,
make
sure
the
TRIGGER
MODE
switch
is
not
set
to
AUTO.
NONTRIGGERED
SWEEP
Ordinarily,
the
displayed
signal
is
also
used
to
trigger
t
he
oscilloscope
sweep.
In
some
situations,
it
may
be
de
sirable
to
reverse
this
situation.
The
sweep-related
output
pulses,
available
from
the
front
panel
of
the
Type
5 3B,
can
be
used
as
a
triggering
signal
for
an
external
device.
The
output
signal
of
the
external
device
can
then
produce
a
stable
display
while
the
oscilloscope
sweep
free
runs.
To
demonstrate
one
method
of
performing
this
operation,
oroceed
as
follows;
Set
the
controls
and
switches
as
follows.
TRIGGER
SLOPE
TRIGGERING
MODE
STABILITY
TIME/CM
+EXT
AC
Fully
clockwise
1
mSEC
Connect
a
lead
from
the
SAWTOOTH
OUT
connector
to
the
vertical
input.
The
display
should
consist
of
a
sloping
line.
The
oscilloscope
display
is
the
sawtooth
pulse
that
is
available
during
each
sweep.
In
a
practical
application,
the
pulse
would
not
be
applied
to
the
vertical
input
but
instead
to
some
external
device
to
be
tested.
The
pulse
would
then
serve
as
the
trigger
pulse
or
input
signal
from
rhe
external
device,
and
the
output
of
the
device
would
provide
a
stable
display
on
the
oscilloscope,
as
though
the
oscilloscope
were
triggered
in
the
normal
manner.
The
—
GATE
OUT
connector
output
signal
of
the
Type
5 3B
can
be
used
as
a
variable
repetition-rate
pulse
gen
erator.
To
use
the
Type
5 3B
in
this
manner,
proceed
as
follows;
Set
the
controls
and
switches
as
follows:
TRIGGER
SLOPE
TRIGGERING
MODE
STABILITY
TIME/CM
+EXT
AC
Fully
clockwise
As
desired
Monitor
the
signal
available
at
the
+
GATE
OUT
con
nector
on
another
oscilloscope
and
establish
the
desired
pulse
repetition
rate
by
setting
the
TIME/CM
and
VARIABLE
controls.
Light
Filter
The
light
filter
provided
with
the
Type
5 3B
minimizes
undesirable
reflections
when
viewing
the
display
under
high
ambient
light
conditions.
The
filter
may
be
left
on
when
taking
waveform
photographs
unless
a
high
writing
rate
is
required.
If
the
light
filter
is
removed,
the
c
rt
protector
plate
should
be
installed
to
prevent
scratches
to
the
c
rt
face
plate.
EXTERNAL
HORIZONTAL
DEFLECTION
For
special
applications,
horizontal
deflection
can
be
produced
with
an
externally
derived
signal.
Thus,
the
oscilloscope
system
can
be
used
to
plot
one
function
against
another
(e.g.
Lissajous
figures).
However,
the
system
is
not
intended
for
precise
phase-angle
measurements.
To
use
an
external
signal
for
horizontal
deflection,
con
nect
the
signal
to
the
EXTERNAL
HORIZ
IN
connector.
Set
the
HORIZONTAL
DISPLAY
switch
to
EXT
and
the
EXTERNAL
HORIZONTAL
VOLTS/CM
con
t
rol
to
0.1,
1
or
10.
The
signal
is
dc
coupled
to
the
deflection
amplifier.
The
time-base
generator
still
controls
rhe
unblanking
of
the
c
rt
display
when
the
HORIZONTAL
DISPLAY
switch
is
set
to
EXT.
To
unblank
the
c
rt
at
a
normal
setting
of
the
INTENSITY
control,
it
will
be
necessary
to
have
the
SINGLE
SWEEP
switch
set
to
NORMAL
SWEEP
and
the
time-base
triggering
controls
set
for
a
free-running
sweep.
If
it
is
undesirable
to
have
the
time-base
generator
running,
then
the
INTENSITY
control
will
have
to
be
turned
up
until
the
beam
is
visible.
DUAL-TRACE
CHOPPED
BLANKING
A
dual-trace
plug-in
unit
provides
two
separate
traces
on
the
c
rt
and
thus
permits
two
functions
to
be
displayed
simultaneously.
Detailed
instructions
for
operating
the
dual
trace
p'ug-in
unit
in
conjunction
with
the
Type
5 3B
Oscillo
scope
are
contained
in
the
plug-in
unit
instruction
manual.
When
the
dual-trace
plug-in
unit
is
operated
in
the
chopped
mode
to
obtain
a
dual-trace
presentation,
switch
ing
transients
will
be
displayed
on
the
c
rt.
These
switching
transients
can
be
reduced
by
placing
the
CRT
CATHODE
SELECTOR
switch
on
the
rear
of
the
instrument
in
the
CHOPPED
BLANKING
position.
INTENSITY
MODULATION
The
Type
5 3B
c
rt
display
can
be
intensity
modulated
by
an
external
signal
to
display
additional
information.
This
is
d
o
ne
by
disconnecting
the
grounding
bar
from
the
EX
TERNAL
CRT
CATHODE
connector
at
the
rear
of
the
instru
ment
and
connecting
the
external
signal
to
this
terminal.
The
CRT
CATHODE
SELECTOR
switch
must
be
in
the
EX
TERNAL
CRT
CATHODE
position.
Very
accurate
time
measurements
can
be
made
by
intensity
modulating
the
beam
with
time
markers
and
measuring
directly
from
the
time
markers
on
the
crt
.
A
positive
signal
of
approximately
20
volts
is
required
to
cut
off
the
beam
from
normal
intensity.
The
low-frequency
cutoff
point
for
Z-axis
modulation
is
600
cps.
2-5
SECTION
3
CIRCUIT
DESCRIPTION
Introduction
This
section
contains
the
theory
of
operation
of
the
various
circuits
in
the
Type
5 3B.
A
simplified
block
diagram
analysis
is
given
first
to
explain
the
operation
of
each
cir
cuit
in
general
terms,
then
the
operation
of
each
circuit
is
covered
in
detail.
BLOCK
DIAGRAM
DESCRIPTION
Low-Voltage
Power
Supply
The
low-voltage
power
supply
produces
all
operating
voltages
for
the
oscilloscope
with
the
exception
of
parts
of
the
c
rt
circuit.
The
low-voltage
supply
provides
regulated
—
150,
+
100,
+225,
+350
and
+500
volts.
It
also
pro
vides
heater
voltages
and
an
unregulated
+325-volt
out
put.
Vertical
Plug-In
Preamplifier
Any
Tektronix
letter-
or
1
-series
vertical
plug-in
preampli
fier
can
be
used
with
the
Type
5 3B.
For
a
circuit
descrip
tion
of
the
plug-in
unit,
refer
to
the
plug-in
unit
instruction
manual.
Vertical
Input
Amplifier
The
vertical
input
amplifier
is
a
balanced
hybrid
ampli
fier
that
amplifies
the
output
of
the
plug-in
vertical
preampli
fier
and
applies
the
amplified
vertical
signal
to
the
trigger
pickoff
circuit
and
the
vertical
output
amplifier.
Delay
Line
The
push-pull
output
of
the
vertical
input
amplifier
is
applied
through
the
balanced
delay
line
to
the
vertical
out
put
amplifier.
The
delay
line
is
a
specially
braided
186
line
which
delays
the
application
of
the
vertical
signal
to
the
vertical
output
amplifier
for
200
nsec.
This
provides
time
for
unblanking
the
crt
and
starring
the
horizontal
sweep
before
the
vertical
signal
reaches
the
deflection
plates.
The
delay
aliows
the
leading
edge
of
a
single
fast-rising
pulse
to
be
displayed.
The
de
l
ay
line
requires
no
adjustment
because
of
the
precision
construction.
Vertical
Output
Amplifier
The
vertical
output
amplifier
is
a
push-pull
cascode
ampli
fier
that
takes
the
output
of
the
delay
line
and
amplifies
it
to
a
level
sufficient
to
drive
the
vertical
deflection
plates
of
the
crt.
Trigger-Pickoff
Circuit
The
trigger-pickoff
circuit
applies
a
sample
of
the
input
waveform
to
the
trigger
circuit
of
the
time
b
a
se.
The
trigger
is
picked
off
at
the
output
of
the
vertical
input
amplifier.
Time-Base
Generator
The
time-base
generator
provides
accurate
ramp
voltages
for
the
horizontal
deflection
system,
unblanking
for
the
crt,
and
a
+
gate
to
the
front-panel
connector.
The
time-base
generator
may
be
triggered
by
signals
derived
from
either
interna!
or
external
sources.
Horizontal
Amplifier
The
input
to
the
horizontal
amplifier
is
selected
from
the
output
of
the
time-base
generator,
or
the
external
horizontal
input
amplifier.
The
selected
input
is
split
in
phase
and
amplified
to
provide
push-pull
drive
to
the
crt
horizontal
deflection
plates.
External
Horizontal
Amplifier
The
external
horizontal
input
amplifier
provides
the
necessary
gain
to
drive
the
horizontal
amplifier
from
external
signals.
An
input
attenuator
and
a
gain
control
provide
horizontal
deflection
factors
from
0.1
to
about
100
volts/cm.
Crt
Power
Supply
The
crt
power
supply
provides
the
high
voltages
for
operating
the
crt.
The
power
supply
is
of
the
rf
type,
using
a
50-kc
Hartley
oscillator.
Secondary
windings
on
the
oscillator
transformer
supply
voltages
to
the
high-voltage
rectifiers.
Cathode-Ray
Tube
(Crt)
The
cathode-ray
tube
used
in
the
Type
5 38
is
a
flat
faced,
internal
graticule,
5-inch
tube
with
6
cm
of
usable
vertical
scan
area.
The
tube
is
designed
for
low-input
capacitance
to
the
vertical
deflection
plates
and
minimum
x-axis
center-to-edge
defocusing.
Calibrator
The
calibrator
in
the
Type
5 3B
is
a
multivibrator
and
cathode
follower
that
provides
a
square-wave
output
with
a
maximum
amplitude
of
100
volts
ai
a
nominal
1
kc.
A
step
a
tt
enuator
permits
switching
the
output
amplitude
from
the
front
panel.
DETAILED
CIRCUIT
DESCRIPTION
The
following
description
is
a
detailed
discussion
of
the
operation
of
each
circuit
in
the
Type
5 3B.
While
reading
through
the
description
of
a
particular
circuit,
refer
to
the
proper
schematic
diagram
in
Section
6.
Low-Voltage
Power
Supply
The
low-voltage
power
supply
in
the
Type
5 3B
(see
Power
Supply
schematic
diagram)
actually
consists
of
five
in-
3-1
Circuit
Descri tion
—
Ty e
543B/RM543B
terrela
t
ed
supplies
that
operate
together
as
a
system.
This
system
delivers
filtered
and
regulated
voltages
of
—
150,
+
100,
+225,
+350,
and
+500
volts
as
well
as
an
un
regulated
dc
voltage
of
+325
volts.
A
common
power
trans
former,
T601,
supplies
the
input
power
to
each
of
the
sup
plies,
as
well
as
heater
power
to
thermal
time-delay
relay
K600
and
the
tubes
in
the
oscilloscope.
Unless
otherwise
specified,
the
Type
5 3B
is
shipped
with
T601
wired
for
1
15-volt
ac
input.
A
connection
diagram
on
the
side
of
the
transformer
shows
alternative
connections
for
other
input
voltages.
An
optional
ac
converter
is
available
to
provide
60-cyclc
power
for
the
fan
motor
if
it
is
desired
to
operate
the
oscilloscope
on
line
frequencies
from
50
to
60
cps
and
00
cps.
The
115-volt
ac
input
power
is
applied
to
T601
through
POWER
ON
switch
SW601.
Overload
protection
is
pro
vided
by
fuse
F601.
Thermal
cutout
TK601
in
the
primary
circuit
of
T601
is
a
protective
device
that
opens
the
trans
former
primary
circuit
if
the
t
emperature
inside
the
oscillo
scope
rises
above
a
safe
level.
TK601
resets
automatically
when
temperatures
return
to
normal;
and
to
shorten
the
cooling
time,
the
fan
continues
to
run
while
TK601
is
open
(except
when
T601
is
connected
for
216-,
230-,
or
2 -volfs
operation).
Therm
al
time-del
a
y
relay
K60C
provides
a
fila
ment
warmup
time
of
approximately
30
seconds
before
the
dc
power
supplies
are
activated.
The
heater
of
K600
is
rated
at
6
volts
and
is
connected
to
6.3
volts
on
the
T601
secondary
winding.
During
heater
warmup
time,
contacts
and
9
of
K600
remain
open.
At
the
end
of
heater
warm
up
time,
contacts
and
9
close
and
apply
power
to
mag
netic
relay
K601
.
Contacts
K601-1
of
K601
remove
the
heater
power
from
K600,
but
bef
ore
K600
can
open,
con
tacts
K601-1
lock
the
holding
circuit
to
the
coil
of
K601.
K601
now
remains
energized
until
the
power
to
the
oscillo
scope
is
switched
off
or
otherwise
interrupted.
When
K601
is
energized,
contacts
K601
-2,
K601-3,
and
K601-
are
also
closed
and
thus
activate
their
respective
dc
supplies.
—
150-Volf
Su ly.
The
—
150-volt
supply
in
the
Type
5 3B
is
the
reference
voltage
source
for
the
other
supplies
and
must
be
very
stable.
The
—
150-volt
supply
includes
a
high-gain
electronic
voltage
regulator
designed
to
give
good
regulation
under
extreme
operating
conditions.
This
regu
lator
circuit
contains
a
series
regulator,
a
glow-discharge
tube
reference
source,
an
error
detector,
and
an
amplifier.
In
operation,
the
input
power
to
the
—
150-volt
supply
is
supplied
by
one
secondary
winding
(pins
6-11)
of
T601.
The
ac
output
of
the
secondary
winding
is
rectified
by
silicon-diode
rectifier
bridge
D6 2
and
filtered
by
C6 0.
In
series
with
the
positive
side
of
the
supply
and
ground
are
series
regulators
V627,
V637
and
V6 7,
paralleled
by
shunt
ing
resistor
R6 7.
The
output
of
the
—
150-volt
supply
is
taken
from
the
negative
side.
Error
sensing
in
the
voltage-regu
:
ator
circuit
is
accom
plished
by
comparator
V62 .
Current
flow
through
V62
is
established
by
the
setting
of
the
tap
on
R61
6
in
the
volt
age
divider
R615,
R616,
and
R617.
The
voltage
on
the
grid
of
V62 A
is
held
at
approximately
—
85
volts
by
reference
stage
V609.
Assuming
that
the
output
voltcge
of
the
—
150-
volt
supply
increases
due
to
increased
line
voltage
or
some
other
cause,
the
vol-age
increase
appears
on
the
cathodes
of
V62
and,
through
the
top
on
R61
6,
on
the
grid
of
V62 B.
Due
to
the
voltage
divider,
only
a
par
of
the
voltage
in
crease
appears
between
the
grid
and
cathode
of
V62 B,
but
the
full
change
appears
on
the
grid
and
cathode
of
V62 A.
The
increase
is
in
the
negative
direction,
therefore
V62 A
increases
its
conduction
to
maintain
the
prope
r
bias
between
grid
and
cathode,
and
this
holds
both
cathodes
more
or
less
fixed
while
the
grid
of
V62 B
is
pulled
negative
by
the
increasing
negative
voltage
across
the
voltage
divider.
The
increasing
negative
voltage
on
the
grid
of
V62 B
causes
a
decrease
in
current;
thus
the
plate
voltage
goes
positive.
The
positive
change
in
plate
voltage
is
amplified
and
in
verted
to
a
negative
change
by
amplifier
V63 .
The
am
plified
error
signal
from
V63
is
applied
to
the
grids
of
series
regulators
,
V637
and
V6 7.
The
negative-going
error
signal
on
the
grids
of
V627,
V637
and
V6 7
decreases
the
current
through
the
tubes,
effectively
increasing
their
resistance
and
the
voltage
drop
across
them.
The
voltage
necessary
to
provide
the
increased
drop
across
the
series
regulator
tubes
and
shunt
resistor
can
only
be
obtained
by
subtracting
it
from
the
negative
side
of
the
supply,
so
the
undesired
increase
in
negative
voltage
is
absorbed
in
the
scries
regulators
and
shunt
resistor.
If
the
output
of
the
—
150-volt
supply
has
decreased
instead
of
increased,
then
the
error
voltage
applied
to
the
grids
of
the
series
regula
tors
would
have
been
positive-going.
The
positive-going
error
voltage
on
the
grids
of
the
series
regulators
would
lower
the
resistance
of
the
series
regulator
tubes,
and
the
voltage
drop
across
them
would
decrease,
leaving
more
voltage
for
the
negative
side
of
the
supply.
Since
the
out
put
voltage
of
the
—
150-volt
supply
depends
upon
the
re
lationship
of
the
voltage
on
the
tap
of
R61
6
and
the
ref
erence
voltage
from
V609,
accurate
adjustment
of
the
out
put
voltage
is
provided
by
making
R616
variable.
Filter
capccitor
C6 0
docs
not
remove
all
the
ripple
from
the
output
of
the
bridge
rectifier,
and
the
series
regulator
circuit
functions
also
to
reduce
this
output
ripple
voltage.
Any
ripple
between
the
—
150-voit
output
point
and
ground
reaches
the
grid
(pin
7)
of
V62 B
via
capacitor
C617.
This
input
ripple
voltage
is
amplified
by
V62
acting
as
a
cath
ode-coupled
amplifier.
The
ripple
output
voltage
at
the
plate
(pin
6)
of
V62 B
has
the
same
polarity
as
the
ripple
voltage
at
the
-150-volt
output.
C628
couples
this
ripple
output
voltage
to
the
grid
of
V63 .
The
ripple
voltage
is
further
amplified
by
V63
and
app
li
ed
to
the
grids
of
the
series
regulator
tubes
with
a
polarity
that
opposes
the
original
ripple
voltage.
Ripple
in
the
positive
side
of
the
—
‘
50-volt
supply
is
coupled
into
a
degenerative
feedback
loop
through
R637
to
the
screen
of
V63 .
Some
of
the
components
in
the
—
150-volt
supply
are
not
necessary
in
norma:
operation
bu-
are
included
to
insure
proper
operation
of
the
circuit
under
adverse
conditions.
R6 0
and
R6 1
protect
against
large
surge
currents,
while
C6 9
suppresses
sudden
load
changes
that
fall
outside
the
bandwidth
of
the
regulator
circuit.
+
100-Volt
Su ly.
Th
e
input
to
the
—
100-volt
supply
is
t
he
output
of
the
secondary
winding
(pins
8-15)
of
trans
former
T601
and
silicon-diode
bridge
D672.
In
addition
to
its
other
loads,
the
+
100-volt
supply
is
required
to
supply
current
to
a
series
string
of
filaments
at
all
times.
When
the
Type
5 3B
is
first
turned
on,
relay
K601
contacts
are
open
and
all
the
regulated
supplies
are
inoperative.
During
this
time,
the
series-string
filaments
arc
supplied
by
the
unregulated
side
of
the
+100
-volt
supply
through
relay
contacts
K601-3
and
R675.
By
the
time
thermal
relay
K600
3-2
Circuit
Descri tion
—
Ty e
543B/RM543B
activates
K601
the
series-string
filaments
have
reached
operating t
empera
t
ure.
When
K601
is
activated
by
K600,
relay contacts
K601-3
shift
the
series-string
filaments
to
the
regulated
output
of
t
he
+
100-volt
supply.
The reference voltage
source
is
t
he
regulated
output
of
the
-150-volt
supply.
V66
is
the
error
amplifier,
and
V677A is the
series
regulator
tube.
The
error-feedback
circuit
is
trough
R650
and
R651,
the
junction
of
which
is
connected to t
he
grid
of
V66 .
The
top
end
of
R650
is
connected to the
regulated
+100-volt
output
and
the
lower
end of
R
6
51
is
connected
to
the
output
of
the
regulated
—
150-volt
supply
to
obtain
reference
voltage.
With
norma!
line voltages
and
loads,
the
voltage
at
the
junction
of
R650
and
R651
is
about
—
1.7
volts
with
reference
to
ground;
this i
s
the
operating
bias
of
V66 .
If the
load
current,
output
voltage,
or
the
input
voltage
changes (inc
uding
changes
due
to
ripple),
the
output
of
the
regulated +
100-volr
supply
starts
to
change
also,
but
any
change
appears
across
R650
and
R651
and
is
applied
to
the
grid
of
V66
as
a
change
in
operating
bi
a
s.
Assuming
that
the
output
of
the
regulated
+
100-volt
supply
tries
to
de-
crease, t
he
reduced
voltage
at
the
top
end
of
R650
permits
the
voltage
a
t
the
junction
of
R650
and
R651
to
go
more
negative
than
the
normal
—
1.7-volt
level
at
that
point.
The i
ncrease
in
negative
bias
on
the
grid
of
V66
reduces
the
flo
w
of
plate
current
through
V66 ,
the
voltage
drop
across
plate-load
resis
to
r
R663
decreases,
and
the
plate
voltage
of
V66
and
the
grid
bias
o
f
V677A
go
more
posi-
rive.
As
the
grid
of
V677A
goes
more
positive,
the
resistance
that
V677A
offers
to
the
flow
of
current
is
decreased
and
the
output
voltage
rises,
compensating
for
the
drop
in
output
voltage
which
initiated
regulating
action.
Of
course,
the
regulator
circuit
can
never
completely
compensate
for
a
change
in
output
voltage,
for
there
must
be
an
error
input
for
the
circuit
to
operate,
but
any
error
in
output
is
reduced
by
a
factor
equal
to
the
loop
gain
of
the
regulator
circuit.
The
screen
grid
of
V66
is
used
as
a
signal
grid
for
in
jecting
a
sample
of
any
rippie
or
transient
voltage
present
in
the
unregulated
side
of
the
+
100-voit
supply
into
the
regulator
circuit.
The
regulator
circuit
t
hereby
becomes
a
dynamic
filter
for
ripple
reduction.
The
ripple
signal
is
applied
to
the
screen
of
V66 ,
amplified
and
inverted
in
phase
by
V664,
then
applied
to
the
grid
of
V677A.
By
the
time
the
amplified
and
inverted
ripple
gets
to
the
grid
of
V677A,
it
is
of
proper
amplitude
and
phase
to
ccncel
out
the
ripple
appearing
at
the
plate
of
V677A.
Unregulated
+325-Volt
Su ly.
The
unregulated
+325-
volt
supply
voltage
source
differs
somewhat
from
the
voltage
source
for
the
—
150-
and
+100-volt
supplies.
A
center
tapped
secondary
on
T601
(pins
5,
7,
10,
and
1
)
and
silicon
diodes
D702
and
D732
form
a
center-tapped
bridge
rectifier
circuit
with
the
negative
side
connected
to
the
positive
un
regulated
side
of
the
voltage
source
for
the
+100-volt
supply.
The
unregulated
+325-voit
output
is
taken
from
the
transformer
center-tap
(pins
7
and
10)
connection.
The
unregulated
output
of
the
voltage
source
for
the
+100-volt
supply
is
approximately
+180
volts.
The
unreg
ulated
output
of
the
center-
tapped
bridge
circuit
is
approx
imately
+
290
volts;
this
added
to
the
unregulated
—
180
volts
provides
the
+
70
volts.
However,
for
the
unregulated
+350-volt
output,
the
connection
is
made
at
the
cerner
tap
(+1 5
volts)
of
the
bridge
(the
midpoint
of
the
+
290
volts).
Adding
the
+180
and
+1 5
volts
provides
the
desired
out
put
of
+325
volts.
+225-Volt
Su ly.
The
voltage
source
for
the
regulated
+225-volt
supply
is
the
unregulated
+325-volt
supply
described
in
t
he
preceding
paragraphs.
The
regulator
circuit
is
similar
to
the
regulator
circuit
found
in
the
—
150-volt
supply;
the
main
difference
being
that
instead
of
using
a
glow
discharge
tube
as
a
reference
voltage
source,
the
reference
voltage
is
from
the
—
150-volt
supply.
The
error
signal
is
picked
off
the
junction
of
precision
resistors
R680
and
R681.
The
upper
end
of
R680
is
connected
to
the
+225-
volt
output,
and
the
lower
end
of
R681
is
connected
to
the
regulated
—
150-volt
supply.
The
voltage
at
the
junction
between
R680
and
R681
is
approximately
0.1
volt
which
is
applied
through
R682
and
R683
to
the
grid
of
V68 B.
The
cathodes
of
V68
are
long
t
ailed
to
the
—
150-volt
supply
through
R685.
The
grid
of
V68 A
is
grounded.
The
error
signal
is
fed
from
the
grid
of
V68 B
through
the
common
cathode
circuit
to
the
A
side
of
the
tube.
Notice
that
this
comparator
is
somewhat
different
from
the
comparator
used
in
the
—
150-volt
supply;
the
output
is
taken
from
the
A
side.
The
error
signal
is
amplified
by
V68
and
fed,
unchanged
and
in
phase,
to
the
voltage
divider
in
the
grid
of
V69 .
V69
also
amplifies
and
inverts
the
error
signal
and
applies
it
out
of
phase
with
any
change
in
the
+225-
volt
output,
to
the
grids
of
series
regulators
V677B
and
V737B.
Here
again,
the
screen
of
the
error
amplifier
is
acting
as
an
injection
grid
for
ripple
reduction.
A
sample
of
the
unregulated
supply
ripple
is
applied
to
the
screen
of
V69 .
V69
amplifies
the
ripple,
inverts
it
in
phase,
and
applies
it
to
the
grids
o
f
series
regulators
V677B
and
V737B.
The
result
is
that
the
same
ripple
appears
simultaneously
on
the
grids
and
plates
of
V677B
and
V737B,
but
180°
out
of
phase,-
thus
the
ripp
l
e
cancels
out.
+350-Volt
Su ly.
The
input
to
the
+350-volt
supply
is
t
he
full
voltage
output
of
the
center-tapped
bridge
(see
description
of
unregulated
+325-volt
supply)
added
to
the
unregulated
side
of
the
+100-volt
supply.
The
operation
of
the
regulator
circuit
is
very
similar
to
the
operation
of
the
-100-volt
regulator
except
for
different
component
values.
+
500-Volt
Su ly.
Rectified
voltage
from
terminals
20
and
21
of
T601
vi
a
D762
is
added
to
the
regulated
voltage
of
the
+350-voit
supply
t
o
supply
the
necessary
voltage
for
the
+500-volt
supply.
The
operation
of
the
regulator
circuit
is
similar
to
that
of
the
+100-vo!t
regulator
except
for
dif
ferent
component
values.
Crt
Circuit
The
crt
circuit
(sec
Crt
schematic
diagram)
includes
the
crt,
the
high-voltage
power
supply,
and
the
controls
neces
sary
to
focus
and
orient
the
display.
The
crt
(Tektronix
Type
T5 70-31
-2)
is
an
aluminized,
5-inch,
flat-faced,
glass
crt
with
a
helical
post-accelerator
and
electrostatic
focus
and
deflection.
The
crt
circuit
provides
connections
for
externally
modu'ating
the
crt
cathode.
The
high-voltage
power
supply
is
composed
of
a
dc-to-50-kc
power
converter,
a
voltage
regulator
circuit,
and
three
high-voltage
outputs.
Front-panel
controls
in
the
crt
circuit
adjust
the
trace
rotation
(screw
driver
adjustment),
intensity,
focus,
and
astigmatism.
In
ternal
controls
adjust
the
geometry
and
high-voltage
output
level.
3-3
Circuit
Descri tion
—
Ty e
543B/RM543B
High-Voltage
Power
Su ly.
The
high-voltage
power
supply
is
an
oscillator
operating
at
approximately
50
kc
with
the
transformer
providing
three
high-voltage
outputs.
The
use
of
a
50-kc
input
to
the
high-voltage
transformer
permits
the
size
of
the
transformer
and
filter
components
to
be
kept
small.
A
modified
Hartely
oscillator
converts
dc
from
the
+325-volt
unregulated
supply
to
the
50-kc
input
required
by
high-voltage
transformer
T801.
C808
and
the
primary
of
T801
form
the
oscillator
resonant
tank
circuit.
No
pro
visions
arc
made
for
precise
tuning
of
the
oscillator
tank
since
the
exact
frequency
of
oscillation
is
not
important.
Voltage
Regulation.
Voltage
regulation
of
the
high-voit-
age
outputs
is
accomplished
by
regulating
the
amplitude
of
oscillations
in
the
Hartley
oscillator.
The
—
1700-volt
out
put
is
referenced
to
the
+
350-vol
t
regulated
supply
through
a
voltage
divider
composed
of
R8 1
,
R8 2,
R8 3,
R8 5,
R8 7,
R853,
and
variable
resistors
R8 0
and
R8 6.
Through
a
tap
on
the
voltage
divider,
the
regulator
circuit
samples
the
—
1700-volt
output
of
the
supply,
amplifies
any
errors
and
uses
the
amplified
error
voltage
to
adjust
the
screen
voltage
of
Harley
oscillator
V800.
If
the
—
1700-volt
output
changes,
the
change
is
detected
at
the
grid
of
V81 B.
The
detected
error
is
amplified
by
V81 B
and
V81 A.
The
error
signal
at
the
plate
of
V81 A
is
direct
coupled
to
the
screen
of
V800
by
making
the
plate-load
resistor
of
V81 A
serve
as
the
screen-dropping
resistor
for
V800.
Any
change
in
the
—
1700-volt
output
thus
changes
the
screen
voltcge
of
V800
and
the
amplitude
of
the
50-kc
oscillations.
R8 0
provides
a
means
of
controlling
the
high-voltage
output
through
con
trolling
oscillation
amplitude.
Crt
Grid
Su ly.
The
approximately
1700-volt
output
of
the
high-voltage
power
supply
is
the
rectified
output
of
one
of
the
two
high-voltage
secondaries
on
T801.
To
provide
dc-coupled
unblanking
signals
to
the
crt
grid,
the
crt
grid
supply
is
floating
(the
dc
voltage
on
the
components
shift
in
accordance
with
the
unblanking
signals).
The
positive
side
of
the
crt
grid
supply
is
returned
to
the
—
1
50-volt
sup
ply
through
the
unblanking
cathode-follower
ioad
resistor
of
the
sweep
generator.
The
negative
side
of
the
crt
grid
supply
is
applied
through
the
INTENSITY
control
to
the
crt
grid.
At
the
fastest
sweep
rates,
the
stray
capacitance
of
the
floating
crt
grid
circuit
makes
it
difficult
for
the
crt
grid
to
rise
fast
enough
to
unblank
the
crt
in
the
required
time.
An
isolation
network
consisting
of
R827,
C829,
and
C830
isolates
the
capacitive
loading.
By
this
arrangement,
the
fast
leading
edge
of
the
unblanking
pulse
is
coupled
through
C830
and
C829
to
the
grid
of
the
crt.
For
short-duration
unblanking
puises,
such
as
those
that
occur
ar
the
fastest
sweep
rates,
the
dc
levels
on
the
rectifier
and
secondary
winding
arc
not
appreciably
affected.
Larger
unblanking
pulses,
such
as
those
that
occur
at
the
slower
sweep
rates,
charge
the
stray
capacitance
in
the
1700-volt
output
through
R827.
This
pulls
up
the
floating
crt
grid
circuit
and
holds
the
crt
grid
at
the
unblanking
potential
for
the
duration
of
the
unblanking
pulse.
+
8300-
and
—
1700-Volt
Out uts.
Both
the
+8300-
and
the
—
1700-volt
outputs
arc
derived
from
the
same
secondary
winding
on
T801.
The
full
secondary
voltage
of
approxi
mately
2900
volts
is
applied
to
a
voltage
tripler
consisting
of
rectifiers
V832,
V8 2,
and
V852
and
associated
capaci
tors.
A
tap
on
the
secondary
provides
the
input
for
half
wave
rectifier
V862
in
the
—
1700-volt
output.
The
—
1700-
volt
supply
is
referenced
to
the
regulated
+350-volt
supply
through
a
voltage
divider
network.
The
+8300-volt
output
is
connected
to
the
crt
post-deflection-accelerator
anode
via
R836
and
the
—
1700-volt
output
is
connected
to
the
crt
cathode,
via
R857
to
provide
a
total
accelerating
voltage
of
10,000
volts.
Crt
Circuit
Controls
and
Connectors.
Optimum
size
and
shape
of
the
fluorescent
spot
on
the
crt
is
obtained
by
ad
justing
the
front-panel
FOCUS
and
ASTIGMATISM
controls.
FOCUS
control
R8 6
provides
the
correct
voltage
for
the
second
anode
(focus
ring)
in
the
crt.
Proper
voltage
for
the
third
anode
is
obtained
by
adjusting
ASTIGMATISM
control
R86 .
To
obtain
optimum
spot
size
and
shape,
both
the
FOCUS
and
ASTIGMATISM
controls
are
adjusted
to
provide
the
proper
electronic
lens
configuration
in
the
region
of
the
second
and
third
anodes
of
the
crt.
Spot
intensity
is
adjusted
by
means
of
front-panel
INTENSITY
control
R826.
Varying
the
INTENSITY
control
changes
the
voltage
on
the
crt
grid,
which
in
turn
varies
the
beam
current.
Internal
GEOMETRY
control
R861
adjusts
the
isolation
shield
voltage
in
the
crt,
and
is
adjusted
to
minimize
"bowing"
or
"tilting"
of
the
display.
Front-panel
TRACE
ROTATION
control
R778
permits
minor
adjustments
in
trace
orientation.
By
adjusting
the
TRACE
ROTATION
control,
the
trace
can
be
made
parallel
with
the
horizontal
lines
on
the
graticule.
An
input
binding
post
on
the
rear
panel
of
the
Type
5 3B
provides
an
input
for
externally
modulating
the
crt
cathode.
The
input
binding
post
is
normally
grounded
by
a
link.
If
it
is
desired
to
intensity
modulate
the
display
from
an
exter
nal
source,
the
link
is
opened,
and
the
modulating
signal
is
coupled
to
the
crt
cathode
through
C858.
When
the
Type
5 3B
is
used
with
a
multichannel
vertical
plug-in
preamplifier
that
provides
dual-trace
chopped
blanking
pulses,
the
blanking
pulses
are
applied
to
rear
panel
CRT
CATHODE
SELECTOR
switch
SW858.
With
the
vertical
plug-in
preamplifier
operating
in
the
chopped
mode
and
SW858
set
to
the
CHOPPED
BLANKING
position
a
positive
pulse
of
approximately
20-volts
amplitude
is
applied
through
C858
to
the
cathode
of
the
crt.
At
normal
intensity
levels,
this
pulse
is
sufficient
to
cut
off
the
crt
during
the
time
the
amplifier
channels
in
the
vertical
plug-in
preampli
fiers
are
being
switched.
Vertical
Amplifier
System
The
vertical
amplifier
system
in
the
Type
5 3B
consists
of
an
appropriate
vertical
plug-in
preamplifier,
a
push-pull
cathode-follower
input
stage,
a
push-pull
hybrid
delay-line
driver,
a
186
delay
line,
and
a
push-pull
hybrid
output
amplifier.
In
addition,
the
trigger-pickoff
circuit
functions
as
a
part
of
the
vertical
amplifier
by
providing
reverse
termina
tion
for
the
delay
line.
Vertical
In ut
Am lifier.
The
push-pull
output
of
the
vertical
plug-in
preamplifier,
with
a
fixed
dc
level
of
ap
proximately
+67.5
volts,
is
applied
to
the
input
of
the
vertical
amplifier
through
terminals
1
and
3
of
the
plug-in
connector.
R 91
and
R 98,
in
series
with
the
grids
of
the
push-pull
cathode-follower
stage,
as
well
as
T500
are
parasitic
sup
pressors.
Input
cathode
followers
V 9 A
and
V 9 B
are
the
two
halves
of
a
6DJ8
twin
triode.
The
cathodes
of
the
3-
Circuit
Descri tion
—
Ty e
543B/RM543B
cathode
followers
are
returned
to
ground
through
vertical
DC
BAL
control
R 95,
which
is
adjusted
to
equalize
the
d
c
voltage
(about
-68.5
volts)
on
the
bases
of
delay-line
driver
transistors
Q51
and
Q52 .
The
DC
SHIFT
control
(R502)
varies
operating
voltage
and
compensates
for
errors
of
thermal
balance
in
Q51
and
Q52
as
well
as
Q58
and
Q59 .
The
balanced
delay-line
driver
stage
is
a
push-pull
cas
code
amplifier
with
an
adjustable
vertical
gain
control
(R520)
connected
in
the
emitter
circuit
of
the
two
transistors.
Gain
is
adjusted
by
controlling
the
amount
of
degeneration
in
the
emitter
circuit
of
the
transistors.
R532
and
R533
set
the
operation
points
of
Q513
and
Q523
which
provide
the
reverse
termination
for
the
delay
line.
The
RC
networks
in
the
collectors
of
Q51 ,
Q52 ,
Q58 ,
and
Q59
set
the
individual
transistor
operating
points
for
thermal
balance.
Vertical
Out ut
Am lifier.
The
vertical
output
amplifier
must
properly
terminate
the
186
delay
line
and
provide
broadband
amplification
of
the
vertical
signals.
The
delay
line
is
properly
termina
t
ed
by
adjusting
C568,
L55 ,
and
L560.
The
output
amplifier
is
a
wideband
amplifier
stage
con
sisting
of
Q58 ,
Q59 ,
V58
and
V59
and
associated
ele
ments.
High-frequency
compensation
in
this
stage
is
pro
vided
by
peaking
coils
L588,
L589,
L598
and
L599
in
the
plate
circuits
of
V58
and
V59 .
The
high-frequency
re
sponse
is
varied
by
adjusting
C581
and
R580,
which
pro
vide
variable
high-frequency
degeneration
in
the
emitter
circuit
of
Q58
and
Q59 .
The
output
stage
of
the
vertical
amplifier
is
a
hybrid
push-pull
cascode
amplifier.
This
circuit
configuration
is
used
to
match
the
low
impedance
of
the
transistorized
verti
cal-amplifier
system
to
the
higher
impedance
required
at
the
c
rt
vertical
deflection
plates.
Trigger-Pickoff
Circuit.
The
trigger-pickoff
transistor
ampli
fier
Q5 3,
not
only
provides
trigger
signals
to
the
time
base,
but
supplies
the
VERT
SIG
OUT
jack
with
a
vertical
signal.
Beam-Position
Indicators.
The
beam-position
indicators
B538
and
B539
driven
by
Q53
and
located
on
the
front
pane!
above
the
ert,
indicate
the
relative
vertical
position
of
the
trace
with
respect
to
the
center
of
the
graticule.
When
the
beam
is
centered
vertically,
the
potential
across
either
neon
is
insufficient
to
light
it.
The
current
through
Q53 ,
and
thus
the
voltage
across
the
neons,
will
change
as
the
beam
is
positioned
up
or
down
on
the
c
rt.
The
voltage
across
one
neon
will
increase,
causing
it
to
light,
and
the
voltage
across
the
other
neon
will
decrease,
causing
it
to
remain
extinguished.
The
neon
that
lights
will
indicate
the
direction
in
which
the
beam
has
been
moved.
Time
Base
The
Time
Base
consists
of
the
sweep
trigger
and
the
sweep
generator
circuits.
The
sweep
trigger
circuit
includes
controls
for
selecting
the
type,
source,
and
level
of
the
trigger
to
be
used,
and
circuit
elements
for
regenerating
the
selected
trigger
into
a
pulse
suitable
for
triggering
the
sweep
generator.
The
sweep
generator
circuit
is
basically
a
Miller
runup
circuit.
The
sweep
generator
provides
ramp
voltages
for
the
horizontal
deflection
system
and
the
SAW
TOOTH
OUT
connector,
unblanking
pulses,
and
+
gate
pulses.
Trigger
Generator.
The
input
to
the
sweep
trigger
circuit
is
selected
by
TRIGGER
SLOPE
switch
SW10A
from
the
trigger-pickoff
circuit
in
the
vertical
amplifier,
the
power
transformer
for
line
triggering,
or
from
rhe
front-panel
TRIG
GER
INPUT
connector.
TRIGGER
MODE
switch
SW10B
permits
further
selection
of
the
type
of
triggering
signal;
either
automatic,
ac
low-frequency
reject,
ac
or
d
c
.
Once
the
type
and
source
of
triggering
signal
has
been
selected,
the
slope
on
which
triggering
is
desired
is
selected
by
TRIG
GER
SLOPE
switch
SW10A.
The
level
of
the
triggering
signal
required
by
the
sweep
trigger
circuit
is
selected
by
adjusting
TRIGGERING
LEVEL
control
R17.
After
this
trig
gering
signal
has
been
selected
by
the
preceding
controls
and
switches,
it
is
applied
to
trigger
input
amplifier
V2 .
The
trigger-input
amplifier
provides
a
source
of
positive
going
signal
to
drive
the
following
stage
and,
by
means
of
the
TRIGGERING
LEVEL
control,
enables
the
operator
to
select
the
point
on
‘
he
signal
at
which
triggered
operation
will
occur.
To
trigger
from
a
positive-going
signal,
the
grid
of
the
V2 A
section
is
connected
to
the
inpu
t
signal
source.
The
grid
of
the
V2 B
section
is
connected
to
a
dc
bias
source,
which
is
adjustable
with
the
TRIGGERING
LEVEL
control.
This
bias
voltage
establishees
the
voltage
present
at
the
plate
under
no-signal
conditions.
The
volt
a
ge
at
the
grid
of
V2 A
and
the
voltage
at
the
plate
of
V2 B
are
in
phase
with
each
other:
that
is,
they
both
go
through
ac
zero
in
the
same
direction
at
the
same
time.
Thus,
the
V2 A
section
acts
as
a
cathode-fol
lower,
and
the
signal
voltage
developed
across
the
cathode
resis
tors
becomes
the
input
signal
to
the
V2 B
section.
To
trigger
from
a
negative-going
signal,
the
grid
of
the
V2 A
section
is
connected
to
the
TRIGGERING
LEVEL
con
trol,
and
the
grid
of
V2 B
is
connected
to
the
input
signal.
With
this
configuration,
the
voltage
at
the
plate
of
the
V2 B
section
will
be
180°
out
of
phase
with
the
input-signal
voltage.
In
each
of
the
cases
outlined
previously,
a
positive-going
signal
is
produced
at
the
plate
of
the
V2 B
section
of
the
Trigger-Input
Amplifier
irrespective
of
the
polarity
of
the
input
signal.
D29
and
D30
are
limiters
and
allow
the
trigger
circuit
to
count
down
to
provide
triggers
at
a
slow
enough
rate
for
the
sweep
gating
multivibrator
to
react.
The
quiescent
voltage
level
on
the
base
of
Q35
is
set
by
the
collector
of
Q3
whose
base
voltage
is
set
by
R39
(TRIG
LEVEL
CENTERING).
The
amplitude
of
the
triggering
signa!
neces
sary
to
cause
operation
of
the
trigger
multivibrator
is
de
termined
by
the
setting
of
the
TRIGGERING
LEVEL
control.
Trigger
amplifier
Q3
provides
additional
amplification
to
the
trigger
signal
before
applying
the
signal
to
the
base
of
Q35.
In
the
quiescent
state,
ready
to
receive
a
signal,
Q35
of
the
trigger
multivibrator
is
conducting
and
the
collector
voltage
is
down.
Since
the
collector
is
dc-coupled
to
the
base
of
the
Q 5,
that
base
is
held
below
cutoff.
With
Q 5
3-5
Circuit
Descri tion
—
Ty e
543B/RM543B
cut
off
its
collector
voltage
is
up
and
no
output
is
devel
oped.
The
negative-going
portion
of
the
signal
from
the
trigger
amplifier
is
required
to
drive
the
base
of
Q35
down.
As
the
Q35
base
is
driven
negative,
the
current
flow
through
the
transistor
is
restricted
and
the
voltage
at
the
collector
starts
to
rise.
The
rise
in
voltage
at
the
collector
of
Q35
corries
the
base
of
Q 5
in
the
positive
direction.
The
emitters
of
both
transistors
are
coupled
together,
and
follow
the
action
of
the
bases.
With
the
Q 5
base
going
in
a
positive
direction,
and
the
emitter
in
a
negative
direc
tion,
Q 5
starts
to
conduct.
As
Q 5
starts
to
conduct,
the
emitters
of
both
transistors
follow
the
action
of
Q 5
base;
hence
the
emitter
voltage
starts
to
rise.
As
the
Q35
base
goes
down
and
its
emitter
goes
up,
it
stops
conducting.
As
Q 5
conducts,
its
voltage
drops,
creating
a
negative
step
at
the
output.
This
transistion
oc
curs
rapidly,
regardless
of
how
slowly
the
base
falls.
When
the
signal
applied
to
the
base
of
Q35
goes
in
a
positive
direction,
the
action
described
in
the
previous
para
graphs
reverses
itself.
That
is,
Q35
will
start
to
conduct
once
more,
while
Q 5
will
be
cut
off.
In
the
AUTO
position
of
the
TRIGGERING
MODE
switch
the
trigger
multivibrator
is
converted
from
a
bistable
con
figuration
to
a
recurrent
configuration.
This
is
accomplished
by
disconnecting
+100
volts
from
the
junction
of
D 9
and
R38,
thereby
allowing
C 9
to
charge
and
discharge.
In
this
mode
of
operation,
the
trigger
multivibrator
will
run
in
the
absence
of
a
triggering
signal.
For
example,
assume
that
the
base
of
Q35
is
just
being
driven
into
cut
off.
The
voltage
at
the
collector
of
Q35
will
rise,
carrying
with
if
the
base
of
Q 5.
As
the
voltage
at
the
base
of
Q 5
starts
to
rise,
Q 5
starts
to
conduct.
The
falling
volt
age
at
the
collector
of
Q 5
is
coupled
to
the
base
of
Q3 .
Since
the
voltage
at
the
base
of
Q3
is
falling,
the
col
lector
voltage
is
rising.
This
rising
collector
voltage
of
Q3
is
then
coupled
to
the
base
of
Q35.
The
base
of
Q3
is
prevented
from
falling
immediately
by
the
action
of
C 9,
which
must
discharge
sufficiently
to
lower
the
voltage
at
the
base
of
Q3
into
cutoff.
As
the
collector
voltage
of
Q3
raises
the
base
of
Q35
sufficiently
to
bring
that
transistor
out
of
cutoff,
its
col
lector
voltage
will
in
turn
lower.
The
lowering
collector
voltage
of
Q35
is
coupled
through
D 3
to
the
base
of
Q 5,
thus
causing
Q 5
to
cut
off.
When
Q 5
reaches
cutoff,
the
circuit
has
completed
one
cycle
of
an
approximately
0-cycle
repetition
rate.
During
calibration,
the
repetition
rate
for
the
AUTO
mode
is
adjusted
by
R 7
(TRIG
SENS),
which
comprises
part
of
the
discharge
path
for
C 9.
Swee
Generator.
The
time-base
generator
consists
of
three
main
circuits:
the
sweep
gating
multivibrator,
the
Miller
runup
circuit,
and
the
holdoff
circuit.
The
time-base
trigger
circuit
furnishes
the
waveform
which
initiates
a
cycle
of
action
in
the
time-base
generator.
Square
waves
from
the
output
of
the
trigger
multivibrator
are
fed
to
the
time-base
generator
where
they
ore
differentiated
and
used
as
trigger
pulses.
To
explain
the
action
of
the
time-base
generator
assume
it
is
in
the
quiescent
state,
just
before
the
arrival
of
a
suitable
trigger
pulse,
with
V135A
conducting.
Square
waves,
generated
by
the
time-base
trigger
cir
cuitry,
are
differentiated
by
the
C131-R131
network.
If
STABILITY
control
R1
10
is
advanced,
the
grid
of
V135A
will
become
more
negative.
As
the
grid
of
V135A
becomes
more
negative,
a
point
is
reached
at
which
a
negative-going
triggering
pulse
from
the
C
1
31
-R1
31
network
will
drive
V135A
into
cutoff.
As
V135A
is
driven
to
cutoff,
the
plate
voltage
rises,
carrying
with
it
the
grid
of
cathode-follower
stage
V135B.
V135B,
used
as
a
cathode
follower
between
the
two
halves
of
the
multivibrator,
isolates
the
positive-going
plate
of
V135A
from
the
capacitance
of
the
loads
requiring
a
posi
tive-going
pulse.
This
results
in
a
faster
rise
of
the
positive
going
pulse
at
t
he
plate
of
V135A.
The
cathode
of
V135B
is
longrailed
through
R1 1
and
R1 3,
and
closely
follows
the
action
of
the
grid.
Since
the
grid
of
V
1
5
has
a
certain
shunt
capacitance
to
ground,
Cl
1
is
connected
in
parallel
with
R1 1
to
compensate
for
this
capacitance.
The
voltage
rise
at
the
cathode
of
V135B
drives
the
grid
of
V
1
5
above
cutoff.
As
VI
5
begins
to
conduct,
its
plate
voltage
drops
rapidly.
Any
spiking
which
may
occur
is
attenuated
by
the
C150-R150
network.
When
V
1
5
is
conducting
at
the
maximum
determined
by
circuit
parameters,
the
sweep-gating
multivibrator
has
reached
its
other
stable
state
and
the
action
of
the
Miller
runup
circuit
has
been
initiated.
The
Miller
runup
circuit
is
essentially
a
Class
A
ampli
fier
employing
negative
feedback.
The
positive-going
volt
age
at
the
plate
of
the
Miller
tube
is
fed
back
to
the
grid
through
runup
cathode
follower
V
1
73
and
opposes
the
attempt
of
rhe
grid
to
go
negative.
Because
the
gain
of
the
Miller
tube
is
high,
(approximately
200)
it
is
possible
to
maintain
an
essentially
linear
rate
of
charge
on
the
tim
ing
capacitor.
In
the
quiescent
state
of
the
time-base
generator,
the
voltage
at
the
plate
of
the
Miller
tube
is
determined
by
the
voltage
drop
across
the
dc
network
formed
by
neon
lamp
B
1
67,
the
runup
cathode
follower,
and
the
discon
nect
diodes.
The
purpose
of
this
dc
network
is
to
establish
a
voltage
at
the
plate
of
the
Miller
tube
of
such
value
that
the
tube
will
operate
above
the
knee,
and
hence
over
the
linear
region
of
its
characteristic
curve.
The
grid
of
Miller
tube
V
1
61
is
returned
to
the
—
150-
volt
supply
through
timing
resistor
R160.
In
the
quiescent
state
of
the
time-base
generator
the
grid
of
the
Miller
t
ube
is
held
slightly
negative,
but
well
above
cutoff,
by
the
flow
of
the
current
through
D
1
50
of
the
disconnect
diodes.
When
the
disconnect
diodes
s
f
op
conducting,
the
grid
of
the
Mill
er
tube
tends
to
become
more
negative.
As
the
grid
of
the
Miller
tube
starts
negative,
the
plate
becomes
more
positive.
This
positive-going
excursion
of
the
p.'ate
carries
the
grids
of
runup
cathode
follower
V
1
73
with
it.
The
voltage
at
the
grids
of
V
1
73
is
maintained
at
a
constant
difference
with
respect
to
the
Miller-tube
plate
voltage
by
the
voltage
drop
across
neon
bulb
B
1
67.
C
1
67
3-6
Circuit
Descri tion
—
Ty e
543B/RM543B
and
R
1
68
form
a
network
connected
around
Bl
67
to
im
prove
the
risetime.
Bootstrap
capacitor
C
1
65
is
connected
between
a
tap
on
the
Miller
tube
plate
load
and
the
cathode
of
V173.
This
bootstrap
capacitor
increases
the
charging
rate
of
the
stray
capacitances
in
the
Miller-tube
plate
circuit.
Its
action
is
most
important
in
the
generation
of
fast
sweep
rates.
The
cathode
of
V
1
73
follows
the
action
of
the
grids
closely.
This
results
in
a
linear
rise
in
the
voltage
at
the
upper
end
of
timing
capacitor
C160.
Since
the
charge
on
the
capacitor
cannot
change
instantaneously,
this
volt
age
is
coupled
to
the
grid
of
the
Miller
tube
in
a
direction
to
correct
for
the
attempt
of
the
Miller-tube
grid
to
go
negative.
Current
to
charge
the
timing
capacitor
is
supplied
through
timing
resistor
R160.
Since
the
voltage
across
the
timing
resistor
is
virtually
constant,
a
constant
current
source
is
thus
provided
for
charging
the
timing
capacitor.
The
linear
voltage
rise
at
the
cathode
of
V
1
73
is
used
as
the
time-base
sawtooth.
This
voltage
rise
continues
until
a
positive
step
from
the
sweep
gating
multivibrator
raises
the
plate
voltage
on
the
disconnect
diodes
to
the
point
where
they
begin
to
conduct.
The
positive-going
voltage
at
the
cathode
of
V
1
73
is
coupled
back
to
the
input
of
the
sweep
gating
multivi
brator
and
causes
that
circuit
to
revert
to
its
other
state.
It
is
kept
from
acting
on
further
trigger
pulses
by
the
ac
tion
of
the
holdoff
circuit.
The
waveform
coupled
to
the
time-base
generator
from
the
time-base
trigger
circuit
contains
both
positive-
and
negative-going
pulses.
To
prevent
a
negative-going
pulse
from
triggering
the
sweep
gating
multivibrator
before
the
action
of
the
time-base
generator
is
completed,
the
grid
of
V135A
must
be
held
above
cutoff.
The
holdoff
circuit
keeps
the
grid
of
V135A
above
cut
off
until
the
capacitances
in
the
time-base
generator
have
had
time
to
reach
their
quiescent
state.
The
point
at
which
the
holdoff
circuit
will
allow
the
sweep
gating
multivi
brator
to
return
to
its
quiescent
state
is
determined
by
the
adjustment
of
R1
76
(SWEEP
LENGTH).
The
sawtooth
present
at
the
cathode
of
the
runup
cathode
follower
is
coupled
to
the
grid
of
V183A
through
R1
76.
During
calibration,
R176
is
adjusted
so
that
the
time
base
terminates
after
it
has
passed
the
right-hand
limit
of
the
graticule.
R176
adjusts
the
voltage
at
the
grid
of
V183A
and
consequently
at
the
cathode
of
V183A
and
also
on
Cl
80,
thus
determining
when
the
sweep
ends.
The
positive-going
pulse
from
the
grid
of
V183A
is
coupled
to
the
cathode
of
V183A
and
the
grid
of
V133B.
The
ac
tion
of
C
1
80
retards
the
voltage
at
the
grid
of
V133B.
The
value
of
C
1
80
is
chosen
so
that
its
capacitance
will
prevent
the
voltage
at
the
grid
of
V133B
from
falling
until
all
capacitances
in
the
time-base
generator
have
returned
to
their
quiescent
level.
Unblanking
Circuit.
In
the
quiescent
state
of
the
time-base
generator,
the
c
rt
beam
is
cut
off.
To
allow
the
c
rt
beam
to
be
seen,
the
potential
at
the
control
grid
of
the
c
rt
must
be
raised.
The
voltage
rise
appearing
at
the
cathode
of
V135B
in
the
time-base
generator
is
used
to
drive
cathode
follower
V183B.
The
signal
on
the
cathode
of
V183B
un
blanks
the
beam
during
the
time
a
sawtooth
is
generated,
permitting
the
left-to-right
motion
of
the
beam
to
be
seen.
The
end
of
the
unblanking
pulse
coincides
with
the
end
of
the
time
base,
and
the
c
rt
is
blanked
during
the
retrace
portion
of
the
sweep
and
during
quiescent
period
of
the
time-base
generator.
Out ut
Waveforms.
The
time-base
sawtooth
from
the
cathode
of
V
1
73
is
fed
through
cathode-follower
V193B
and
is
available
at
the
SAWTOOTH
OUT
front-panel
con
nector.
The
same
pulse
that
is
fed
to
the
grid
of
V
1
83
B
for
un
blanking
purposes
is
also
fed
to
cathode-follower
V193A
which
makes
the
pulse
available
at
the
-GATE
OUT
front
panel
connector.
Single
Swee
Circuit.
When
the
SINGLE
SWEEP
switch
is
in
the
center
position,
plate
voltage
is
applied
to
V133A
and
this
tube
operates
in
conjunction
with
V
1
25
as
a
bi
stable
multivibrator.
In
the
first
stable
state
after
the
completion
of
a
sweep,
V125
is
cut
off
and
V133A
is
conducting.
In
this
state,
the
divider
between
the
plate
of
V
1
25
and
the
grid
of
V133A
sets
t
he
cathode
voltage
of
the
lockout
multivi
brator
and
consequently
the
grid
voltage
of
V135A.
LOCK
OUT
LEVEL
ADJ
R125
is
adjusted
to
set
the
grid
of
V135A
high
enough
so
that
the
sweep
gating
multivibrator
cannot
be
triggered;
this
locks
out
the
sweep.
Placing
the
SINGLE
SWEEP
switch
to
the
RESET
posi
tion
grounds
C
1
22.
This
causes
a
sharp
drop
in
the
plate
voltage
of
V
1
25.
The
drop
in
the
plate
is
fed
through
the
divider
between
the
plate
of
V
1
25
and
the
grid
of
V133A
and
forces
the
lockout
multivibrator
into
its
other
stable
state
with
V
1
25
conducting
and
V133A
cut
off.
With
V133A
cut
off,
its
plate
voltage
rises
and
ignites
the
READY
light.
With
V
1
25
conducting,
the
STABILITY
control
regains
con
trol
over
the
grid
level
of
V135A.
Depending
on
the
adjustment
of
the
STABILITY
control,
a
sweep
can
now
be
produced
in
one
of
two
ways.
If
the
STABILITY
control
is
turned
fully
clockwise,
the
grid
of
V135A
will
be
pulled
down
and
cause
the
sweep
gating
multivibrator
to
switch
to
its
other
state
and
initiate
a
sweep.
Or,
if
the
STABILITY
control
is
adjusted
for
trig
gered
operation,
the
sweep
will
be
initiated
by
the
first
negative
trigger
pulse
to
arrive
at
the
grid
of
V135A.
As
the
sweep
begins,
the
rising
sawtooth
voltage
pulls
up
the
cathode
of
V
1
33
B
by
the
holdoff
action
previously
described.
As
the
cathode
of
the
lockout
multivibrator
follows
the
cathode
of
V133B
up,
V
1
25
cuts
off
and
V133A
conducts.
As
the
cathodes
continue
to
rise
(following
the
rise
in
the
sawtooth
sweep
voltage)
V133A
cuts
off
again.
Both
tubes
are
then
held
cut
off
for
the
remainder
of
the
sweep
and
the
READY
light
stays
on.
When
the
grid
of
V135A
rises
to
the
point
at
which
the
sweep
gating
multi
vibrator
reverts,
the
sweep
is
terminated.
As
hold-off
capacitor
C
1
80
discharges,
the
cathodes
of
the
lockout
multivibrator
start
to
fall.
The
grid
level
of
V133A
is
such
that
this
tube
comes
out
of
cutoff
first,
thus
V133A
conducts
and
V
1
25
remains
in
cutoff.
As
V133A
3-7
Circuit
Descri tion
—
Ty e
543B/RM543B
conducts,
its
plate
drops
and
extinguishes
the
READY
light.
A
new
sweep
cannot
be
initiated
until
the
SINGLE
SWEEP
switch
is
again
pressed
to
the
RESET
position,
Dual-Trace
Sync
Pulse
and
Cho ed
Blanking
Circuitry.
Synchronizing
pulses
for
dual-trace
plug-in
preamplifiers
are
supplied
by
V15 B.
When
multivibrator
V1 5
cuts
off,
a
sharply
differentiated
positive
pulse
is
developed
at
its
screen.
This
pulse,
coupled
to
the
grid
of
V15 B,
produces
a
negative
trigger
at
the
plate
of
V15 B.
This
trigger
then
switches
the
multivibrator
in
the
dual-trace
unit
employed
for
alternate
sweeps.
When
the
dual-trace
multivibrator
is
connected
for
free-
running
operation
to
produce
chopped
sweeps,
a
negative
pulse
is
coupled
from
the
multivibrator
to
the
grid
of
V15 A.
The
resultant
positive
pulse
at
the
plate
of
V15 A
is
coupled
to
the
cathode
of
the
crt
to
blank
out
the
beam
during
switching.
Refer
to
the
dual-trace
plug-in
unit
instruction
manual
for
a
detailed
description
of
the
switching
opera
tion.
Horizontal
Amplifier
The
Horizontal
Amplifier
converts
the
single-ended
saw
tooth
output
of
the
time-base
generator
into
a
push-pull
signal
suitable
for
driving
the
horizontal
plates
of
the
c
r
t
.
The
dc-coupled
Horizontal
Amplifier
consists
of
a
cathode
follower
input
stage,
two
stages
of
push-pull
amplification
and
a
cathode-follower
output
stage.
The
gain
of
input
amplifier
V35 -V36
is
controlled
by
negative
feedback
applied
from
the
cathodes
of
the
output
of
stage
V37 B-
V38 B.
The
amount
of
negative
feedback
applied
to
the
input
amplifier,
and
hence
the
gain
of
the
amplifier,
is
determined
by
the
setting
of
the
HORIZONTAL
DISPLAY
switch.
As
the
magnification
factor
is
increased
the
gain
is
increased
by
decreasing
the
feedback.
Input
Amplifier
The
positive-going
sweep
sawtooth
voltage
produced
by
the
time-base
generator
circuit
is
coupled
through
a
frequency-compensated
voltage
divider
to
the
grid
of
input
cathode
follower
V3 3.
The
attenuation
of
the
divider
can
be
altered
slightly
by
the
adjustment
of
R3 2
XI
CAL.
The
small
time-constant
network
C339-R339
inproves
the
start
of
the
waveform
at
the
faster
sweep
rates.
The
two
positioning
controls,
HORIZONTAL
POSITION
R3 0
and
VERNIER
R3 6,
affect
the
beam
positioning
by
altering
the
de
level
at
the
grid
of
V3 3.
The
voltage
and
resistance
values
in
the
positioning
circuits
are
such
that
the
VERNIER
can
move
the
spot
about
1
cm
while
the
HORIZONTAL
POSITION
control
can
move
the
spot
about
10
cm
when
the
HORIZONTAL
DISPLAY
switch
is
in
the
NORMAL
(XI)
position.
Because
of
their
low
impedance,
on
adjustment
of
the
positioning
controls
does
not
materially
alter
the
attenuation
of
the
divider
network.
Input
amplifier
V35 -V36
is
a
cathode-coupled
phase
inverter;
the
positive-going
sawtooth
at
the
grid
of
V36
is
converted
to
a
push-pull
sawtooth
at
the
plate
circuits
of
V35
and
V36 .
The
impedance
network
connected
between
the
two
cathode
circuits
plays
an
important
role
in
determining
the
amount
of
negative
feedback
applied
to
the
input
amplifier.
Two
of
the
components
in
this
network,
R361
and
C361,
have
their
value
selected
by
the
HORIZONTAL
DISPLAY
switch.
The
negative
feedback
which
comes
from
the
output
cathode
follower
stage
is
applied
through
a
frequency-compensated
divider
consisting
of
R387-C387
on
one
side
and
R388-C388
on
the
other,
and
the
impedance
connected
between
the
cathodes
of
the
input
amplifier.
The
smaller
the
impedance
connected
between
the
two
cathodes
the
greater
the
drop
across
the
series
components
and
the
less
the
amount
of
feedback
applied
to
the
input
amplifier.
Derails
of
the
R361-C361
network
are
shown
in
the
switch
layout
on
the
Horizontal
Amplifier
diagram.
In
the
X100
SWEEP
MAGNIFIER
position
of
the
HORI
ZONTAL
DISPLAY
switch,
R361
and
C361
are
replaced
with
very
small
impedance.
This
decreases
the
negative
feedback
and
increases
the
gain
of
the
stage
100
times
over
that
of
the
NORMAL
(X
1
)
position
of
the
switch.
X
1
00
CAL
R375
is
adjusted
so
that
the
stage
gain
in
the
X
1
00
SWEEP
MAGNIFIED
position
of
the
HORIZONTAL
DIS
PLAY
switch
is
100
times
that
of
the
NORMAL
(X
1
)
posi
tion.
The
X
1
CAL
control
R3 2
is
adjusted
to
attenuate
the
input
signal
so
that
the
Horizontal
Amplifier
has
the
desired
amount
of
deflection
in
the
NORMAL
(X
1
)
position
of
the
HORIZONTAL
DISPLAY
switch.
To
adjust
for
the
dc
shift
in
V35
which
is
caused
by
thermal
changes
in
the
tube,
a
dc
shift
network
consisting
of
C36 ,
R36
and
R365
is
connected
between
the
cathode
of
V37 B
and
the
input
grid
of
V35 .
The
dc
shift
network
provides
positive
feedback
to
V35 ;
the
amount
of
posi
tive
feedback
is
controlled
by
adjusting
DC
SHIFT
R365.
When
the
DC
SHIFT
control
has
been
properly
set,
the
start
of
the
trace
will
remain
constant.
SWP/MAG
REGIS
R359
is
adjusted
to
preserve
the
d
c
balance
of
the
amplifier
as
the
degeneration
networks
in
the
cathode
circuit
of
the
input
amplifier
are
changed.
This
will
insure
that
the
portion
of
the
trace
in
the
exact
center
of
the
crt,
when
the
HORIZONTAL
DISPLAY
switch
is
in
the
NORMAL
(X
1
)
position,
will
be
expanded
sym
metrically
about
the
center
when
the
switch
is
moved
to
any
of
the
SWEEP
MAGNIFIED
positions.
Two
MAGNIFIER
neon
glow
lamps
are
located
on
the
front
panel
immediately
below
the
HORIZONTAL
DISPLAY
switch;
circuitry
for
the
lamps
is
shown
in
the
switch-detail
on
the
Horizontal
Amplifier
schematic.
The
MAGNIFIER
ON
lamp
lights
whenever
the
HORIZONTAL
DISPLAY
switch
is
in
any
of
the
SWEEP
MAGNIFIED
positions.
The
MAGNIFIER
UNCALIBRATED
lamp
is
connected
to
light
whenever
the
sweep
rate
exceeds
the
maximum
calibrated
rate
of
0.02
sec/cm.
This
lamp
will
not
light
as
long
as
the
setting
of
the
TIME/CM
switch,
divided
by
the
mag
nification
factor,
is
not
faster
than
0.02
µsec.
Output
Amplifier
The
positive
feedback
fed
output
amplifier
stage
V37 A-
V38 A
operates
as
a
conventional
high
gain,
push-pull,
plate
loaded
amplifier.
The
cathode
followers
V37 B-V38 B
provide
a
high-impedance,
low-capacitance
load
to
help
keep
the
gain
of
the
stage
constant
over
the
sweep
range
of
the
instrument.
The
cathode
followers
also
provide
the
necessary
low-impedance
output
to
drive
the
capacitance
of
the
horizontal
deflection
plates.
Bootstrap
capacitors
C378
and
C382
improve
the
response
at
the
faster
sweep
rates
by
supplying
additional
current
from
the
output
3-8
Circuit
Descri tion
—
Ty e
543B/RM543B
cathode
follower
stage
to
charge
and
discharge
the
stray
capacitance
in
the
plate
circuit
of
the
output
amplifier.
The
positive
feedback
network
of
C368,
R360,
R367,
R368,
R369
and
R370
gives
the
output
amplifier
its
extremely
high
gain.
This
network
is
connected
between
the
cathode
of
V37 B-V38 B
and
the
input
grid
of
V37 A-V38 A.
C368
is
adjustable
so
that
the
feedback
network
will
provide
the
same
impedance
ot
each
plate
of
the
driver
stage.
At
the
faster
sweep
rates
the
current
through
the
output
cf
tubes
is
too
small
to
discharge
the
capacitance
of
the
horizontal
deflection
plates
and
their
associated
wiring
at
the
required
rate.
Additional
current
for
this
purpose
is
provided
by
the
gated
pentode
V39
connected
to
the
cathode-return
circuit
of
V37 B.
This
permits
the
cathode
of
V37 B,
the
negative-sawtooth
cathode
follower,
to
run
down
at
the
required
rate.
A
similar
current
boost
is
not
required
for
V38 B
since
this
tube
is
the
positive-sawtooth
cathode
follower
and
the
cathode
runs
down
during
the
retrace.
Because
the
plate
current
of
a
pentode
is
fairly
constant
over
a
large
range
of
plate
voltage,
the
cathode
current
of
V37 B
will
remain
nearly
constant
even
though
its
cath
ode
falls
about
100
volts
during
the
trace
portion
of
the
negative
sweep
waveform.
The
additional
current
required
for
faster
sweep
rates
is
obtained
by
applying
a
positive
flat-topped
pulse
to
the
grid
of
the
pentode
V39
during
the
period
of
the
sweep.
This
pulse
is
derived
by
differentiating
the
positive-going
sawtooth,
available
at
the
cathode
of
V38 B,
in
C39
and
the
resistance
in
the
grid
circuit
of
V39 .
The
amplitude
of
the
pulse
is
proportional
to
the
slope
of
the
sawtooth,
and
thus
proportional
to
the
sweep
rate.
Beam-Position
Indicators.
The
beam-position
indicators
B380
and
B390
located
on
the
front
panel
above
the
crt
indicate
the
relative
horizontal
position
of
the
spot
or
center
of
the
trace
with
respect
to
the
center
of
the
graticule.
When
the
spot
or
trace
is
centered
horizontally,
the
po
tential
across
either
neon
is
insufficient
to
light
it.
As
the
beam
is
positioned
left
or
right
on
the
crt,
the
voltage
across
the
neons
will
change.
The
voltage
across
one
neon
will
increase,
causing
it
to
light,
and
the
voltage
across
the
other
neon
will
decrease,
causing
it
to
remain
extin
guished.
The
neon
that
lights
will
indicate
the
direction
in
which
the
spot
or
trace
has
been
moved.
External
Horizontal
Am lifier.
The
setting
of
the
EXTER
NAL
HORIZONTAL
VOLTS/CM
switch
determines
whether
the
signal
is
directly
coupled
to
the
grid
circuit
of
V32 A,
or
whether
one
or
two
frequency-compensated
attenuators
is
connected
to
the
signal
path.
For
all
positions
of
this
switch
the
input
impedance
is
1
megohm
shunted
by
approx
imately
3
pf.
The
External
Horizontal
Amplifier
V32
operates
as
a
cathode-coupled
amplifier.
V32 A
is
the
cathode
follower
and
V32 B
is
the
grounded-grid
stage.
VARIABLE
control
R325
provides
a
means
for
adjusting
the
gain
over
a
10
to
1
range.
EXT
HORIZ
DC
BAL
control
R33
adjusts
the
de
level
of
V32 B
so
that
its
cathode
will
be
at
the
same
voltage
as
the
cathode
of
V32 A
when
no
signal
is
applied
to
the
grid
of
V32 A.
With
the
cathode
at
the
same
volt
age
there
will
be
no
current
through
VARIABLE
control
R325.
By
this
arrangement
an
adjustment
of
the
VARIABLE
gain
control
will
not
change
the
dc
level
at
the
plate
of
V32 B
and
therefore
will
not
affect
the
positioning
of
the
beam.
The
gain
of
the
Horizontal
Amplifier,
when
connected
to
the
External
Horizontal
Amplifier,
is
calibrated
by
means
of
EXT
HORIZ
AMP
CAL
control
R361M,
shown
on
the
switch
layout
section
of
the
Horizontal
Amplifier
diagram.
R361M
is
adjusted
so
the
horizontal
deflection
will
agree
with
the
setting
of
the
EXTERNAL
HORIZONTAL
VOLTS/CM
switch
when
the
VARIABLE
control
is
turned
fully
clockwise
to
the
CALIBRATED
position.
Amplitude
Calibrator
The
amplitude
calibrator
is
a
square-wave
generator
with
approximately
a
1
-kc
output
available
at
the
front
panel
CAL
OUT
connector.
The
amplitude
calibrator
con
sists
of
multivibrator
V875
and
V885A
connected
to
switch
cathode
follower
V885B
between
two
operating
states:
cut
off
and
conduction.
During
the
negative
portion
of
the
multivibrator
wave
form,
the
grid
of
V885
B
is
driven
well
below
cutoff
and
its
cathode
rests
at
ground
potential.
During
the
positive
portion
of
the
waveform,
V875
is
cut
off
and
its
plate
rests
slightly
below
+100
volts.
The
cutoff
voltage
at
the
plate
of
V875
is
determined
by
the
setting
of
CAL
ADJ
control
R879;
part
of
the
divider
connected
between
+100
volts
and
ground.
Cathode-follower
V885B
has
a
precision
tapped
divider
for
its
cathode
resistor.
When
the
CAL
ADJ
control
is
properly
adjusted,
the
cathode
of
V885B
is
at
+100
volts
when
V875
is
cut
off.
18
output
voltages
from
0.2
mvolts
to
100
volts
are
available
through
tapped
divider,
R885-
R893,
and
1000/1
divider
R896-R897.
C885,
connected
be
tween
the
cathode
of
V885B
and
ground,
connects
the
out
put
waveform
for
overshoot.
The
amplitude
calibrator
provides
a
0.1
-volt
output
when
the
AMPLITUDE
CALIBRATOR
switch
is
set
to
0.5
volt
and
a
50-
load
is
connected
to
the
CAL
OUT
connector.
3-9
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